TECHNICAL FIELD

This disclosure relates to the field of wireless power transmission.

BACKGROUND

[0001] As is known in the art, wireless power transmission refers to the transmission of electrical energy from a source to a load without the use of physical (e.g. mechanical) signal paths or connectors between the source and load. In some wireless transfer systems, an antenna radiates radio waves from the source to a load.

SUMMARY

[0002] Disclosed herein are concepts, systems and methods for wireless power transmission via radiative or far-field techniques.

[0003] In a first aspect, the concepts, systems and methods described herein related to wireless power transmission systems can include a conductive waveguide at least partially filled with a dielectric material, the waveguide extending along a first direction (e.g., z-axis) from a first end to an opposing end thereof, the waveguide having a bottom face, a top face and a pair of side faces that together form a substantially rectangular cross-section of the waveguide, the top face having a plurality of slots oriented substantially orthogonal to the first direction and distributed between the first end and the opposing end, the slots separated from each other by a first distance (li) measured along the first direction. The waveguide can include a plurality of barriers interleaved with the plurality of slots, the barriers separated from each other by the first distance, each of the barriers extending between the top and bottom faces and having a barrier cross-section with an area smaller than an area of the waveguide cross-section. The system can also include an input port coupled with the first end of the waveguide, the input port configured to receive an input waveform to be guided by the waveguide. [0004] Embodiments of the wireless power transmission systems can include any one or more of the following features,

[0005] Each of the side faces can include a plurality of conductive vias distributed from the first end to the opposing end, and each of the barriers can include two conductive vias spaced apart from each other by a second distance ($2} measured orthogonal to the first direction, and from an adjacent slot by a third distance {½) measured along the first direction.

[0008] Each of the side faces can include a conductive plate extending from the first end to the opposing end, and each of the barriers can include two conductive plates arranged orthogonally to the respective side faces and separated from each other by a second distance (s ₂ ) and from an adjacent slot by a third distance (fe).

[0007] The waveguide cross-section can be configured to cause the

waveguide to guide, from the first end to the opposing end, the input waveform having a frequency (fi) in a target frequency range (e.g., 5.8 ± 0.075 GHz), and a combination of the first distance ( ), the second distance (S2) and the third distance (l ₂ ) can be configured to cause an output wave having the frequency of the input waveform to exit the waveguide through the plurality of slots along a propagation direction that forms a first angle (90-QH), relative the first direction, associated with the frequency of the input waveform.

[0008] The conductive waveguide can include a metal or a conductive polymer. The dielectric material can include low electrical loss material. The dielectric material can include ceramic, glass, po!ytetraf!uoroethylene, polycarbonate or acrylic.

[0009] The input port (130) can include a coaxial cable connector. The input port can further include impedance matching circuitry.

[0010] The system can include a waveform source coupled with the input port to provide the input waveform to the input port. [001 1] The system can include a plurality of waveguides arranged along the first direction (e.g., the z-axis), and separated from each other by a predetermined separation (δ) measured orthogonal to the first direction, and a plurality of input ports coupled with the first end of each of the respective waveguides, each of the input ports configured to receive a respective input waveform Τι ,φ to be guided by the associated waveguide,

[0012] The input waveforms (f1 ,φ ) applied at the input ports can have the same frequency (fj) and corresponding phases (φ,, where i~1 ... N ₂ ), and a combination of the phases and the predetermined separation between the waveguides can be configured to cause the output wave (f-i ) to exit the

waveguides through the slots along a propagation direction that has a first component that forms the first angle (90~Oi ) with the first direction (e.g., in the y-z piane) and a second component that forms a second angle (βι) relative to a direction orthogonal to the first direction (e.g., in the x~y plane).

[0013] In another aspect, the disclosure features methods for wireless power transmission (see FIG. 1 A) including receiving, at an antenna, a first input waveform having a first frequency (f-j), wherein the antenna comprises a first I D- array of resonance cavities that (i) are coupled with their adjacent cavities through partially transmissive barriers, and (ii) have respective slots arranged orthogonally to a first direction that is parallel to the first 1 -D array of resonance cavities, wherein the first input waveform is received at a first input port coupled to a first resonance cavity of the first I D-array of resonance cavities, guiding the first input waveform through the first 1 D-array of coupled resonance cavities, radiating a first output wave having the first frequency of the first input waveform through the slots along a propagation direction that forms a first angle (90-αι), relative the first direction, the first angle being associated with the first frequency of the first input waveform.

[0014] Embodiments of the methods can include any one or more of the following features.

[0015] The methods for wireless power transmission can include receiving, at the first input port a second input waveform having a second frequency (fa) different from the first frequency (fi} _: guiding the second Input waveform through the first I D-array of coupled resonance cavities, radiating a second output wave having the second frequency of the second input waveform through the siots aiong another propagation direction that forms a second angle (80-02), relative the first direction, the second angle being different from the first angle ( -.) and associated with the second frequency of the second input waveform.

[0016] The methods can include receiving, at a plurality of input ports that includes the first input port, first input waveforms fi , >j) having corresponding phases (φ;), wherein the input ports are coupled with respective 1 D-arrays of coupled resonance cavities that include the first 1 D~array of coupled resonance cavities, the I D-arrays of coupled resonance cavities being parallel to each other and separated from each other by a predetermined separation (δ), guiding the first input waveforms through the respective 1 D-arrays of coupled resonance cavities, and radiating the first output wave through the slots along another propagation direction that has a first component that forms the first angle (90-αι) relative the first direction (e.g., in the y-z plane), and a second component that forms another angle (β-ι) relative to a. direction orthogonal to the first direction (e.g., in the x-y plane).

[001 7] In accordance with a further aspect of the concepts, systems and techniques sought to be protected herein, it has been recognized that many currently explored schemes for radiative wireless power transfer use either 2.4 GHz or 5.8 GHz frequencies. In order to transfer power over substantial distances with an acceptably low divergence angle (so that the efficiency would not be unacceptably low), the sources (transmitters) have to be fairly large. The

divergence angle scales as D/Λ, where D is the linear size of the source, and A is the wavelength of the wave used to transmit the power. The size of the source scales as D ² , so the penalty for using low wavelength is quite steep. For a frequency of 5.8 GHz, the wavelength Λ is about 5 cm.

[0018] In contrast, schemes which propose to rely on ultra-sound for wireless power transfer, can have (for a given divergence angle) much smaller sources, simply because their wavelength is much smaller. For example, if fsouND~60 kHz, this corresponds to AsoLf o~ .5cm, or 10x smaller than the electromagnetic (EM) wave scheme which uses f=5.8 GHz. So, the transmitters used by ultrasound schemes could in principle be OOx smaller (in area) due to the smaller

wavelength. However, the technology for converting energy into ultrasound (and back) is much less mature compared to the EM counterparts.

[0019] it has thus been recognized that the concepts system and techniques described herein may be used at higher frequencies (e.g. frequencies of about 30 GHz or about 60 GHz _; or even higher). At 60 GHz, an EM wavelength will be about 0.5 cm, so one may capture many of the theoretical benefits of ultrasound (small wavelength). However, the technology to convert energy into EM waves at 30-60 GHz (and back) is much more mature. One reference on state-of-the-art of such conversion may be found at: htip;//reposjtoiy- kuiib. kyoto- u.ac.jp/dspace/bttstream/2433/179775/1 /elex.10.20132GG9.pdf

BRIEF DESCRIPTION OF THE PROPOSED DRAWINGS

[0020] FIG. 1 A is a schematic diagram of an antenna for wireless power transmission.

[0021] FIG, 1 B is a schematic diagram of an antenna system for wireless power transmission.

[0022] FIG. 2A is a top plan view of a waveguide antenna for wireless power transmission.

[0023] FIG. 2B Is a top perspective view of an end portion of the waveguide antenna of FIG. 2A.

[0024] FIG. 2C is a top perspective view of an end portion of the waveguide antenna of FIG. 2A.

[0025] FIG. 2D is a bottom perspective view of the end portion of the

waveguide antenna shown in FIG. 2B. [0028] FIG. 2E is a bottom perspective view of the end portion of the waveguide antenna shown in FIG. 2C.

[0027] FIG. 3A is a top plan view of an antenna for wireless power

transmission.

[0028] FIG. 38 is a top perspective view of an end portion of the waveguide antenna of FIG. 3A.

[0029] FIG. 3C is a top perspective view of an end portion of the waveguide antenna of FIG. 3A.

[0030] FIG. 3D is a bottom perspective view of the end portion of the waveguide antenna of FIG. 3B.

[0031] FIG. 3E is a bottom perspective view of the end portion of the waveguide antenna of FIG. 3C.

[0032] FIG. 4A is a fop plan view of an antenna for wireless power reception,

[0033] FIG. 4B is a top plan view of a frequency selective surface for a wireless power receiver.

[0034] FIG. 4C is a diagram of a receiver system.

DETAILED DESCRIPTION

[0035] Disclosed are concepts, systems and methods in the field of beam steering antennas for radiative energy transfer. In illustrative embodiments, the antenna can be a coupled-cavity waveguide (CCW) having a series of unit ceil resonators that are weakly coupled to each other. Depending on how strongly the resonator unit cells are coupled, the range of frequencies (the bandwidth) that can propagate through the waveguide can vary. Each of these frequencies can radiate an electromagnetic beam at different angles, allowing the antenna to steer the beams. In embodiments, the antenna can generate wide beam steering within a small frequency bandwidth, for example, of approximately 5.3 ± 0.075 GHz. In embodiments, this antenna configuration can provide for a low-cost method of

5 steering as compared to a traditional phased antenna array that may require phase-shifting components in addition to the frequency source.

[0038] Referring now to FIG, 1 A. an antenna 100 for wireless power transmission includes a conductive waveguide 110 having a dielectric material 115 disposed therein. In embodiments, the waveguide may be uniformly filled with the dielectric material, for example, Taconic R.F-35TC, made primarily of a ceramic filled material reinforced with glass fabric (PTFE). In other embodiments, the waveguide may be partially filled with a dielectric. In still other embodiments, the waveguide may be air filled. [0037] The waveguide may be provided, for example, from an electrically conductive material such as a metal, such as copper, or a conductive polymer. The waveguide has a bottom face (or walls or surface) 112, a top face (or wails or surface) 114, and a pair of side faces (or walls or surfaces) 116a, 116b, which together form a waveguide having a rectangula cross-section. In embodiments, the waveguide can have rounded edges (e.g. rounding which may occur during the course of a normal manufacturing process. The waveguide 110 has a length L a width D and a thickness (or height) T. The top face 114 has a plurality of slots here N i slots 118a-118 i, generally denoted 118 oriented along the x-axis (i.e. substantially transversely disposed relative to the direction of signal propagation in the waveguide). In this illustrative

embodiment, slots 118 are distributed from a first end 111 a of the waveguide 110 to an opposing end 111 b thereof (along the z-axis), and separated from each other by a distance h (measured along the z-axis). ft should be appreciated that the slots are preferably tilted with respect to the transverse direction, but the spacing between them should preferably be substantially constant.

[0038] The waveguide 110 has a plurality of partially transmissive barriers 120 that are spaced from each other by the distance . It should be appreciated that the barriers are meant to reduce the cross-sectional area of each resonant cavity. In this manner, the barriers 120 form a plurality of resonant cavities 122, each resonant cavity 122(j) coupled to its adjacent resonant cavities 122(j-1) and 1220+1 ). [0039] Each barrier 120 is separated from an adjacent slot 118 by a distance b. In this manner, the Ν·ι barriers 120 are interleaved with the i slots 1 18, or equivalent!^ each of the coupled resonant cavities 122 has an associated slot 1 18. The antenna 100 also includes an input port 130 coupled with the first end 1 1 a of the waveguide 1 10. The input port 130 includes a coaxial cable connector 132. The input port 130 may optionally include impedance matching circuitry 134. In embodiments, the impedance matching circuitry 143 can include a tunable element such as a tunable capacitor. It should, of course, be appreciated that elements having capac!tive or inductive characteristics (e.g. capacitors and/or inductors) can be used as tunable elements. The tunable element can vary (or tune) the operating frequency. The inclusion of a tunable element can thus allow for the use of a single frequency source instead of a variable frequency source.

[0040] In embodiments, changing the material (i.e. changing the manner in which the waveguide is loaded or changing properties of the material with which the waveguide is loaded can cause the need to scale the waveguide. The wavelength of the input waveform depends at least in part, upon on the dielectric constant of the substrate (in this case, the dielectric materia!) used in the waveguide: c

(Eq,

f 1) where Eq. 1 describes the wavelength /1 ₀ in free space (defined by speed of light c in free space) and the frequency of the input waveform and where Eq. 2 describes the wavelength A _su&5tra£e in a substrate (defined by a relative dielectric constant or relative permittivity e _r ). The wavelength of the waveform in the substrate used can be used to determine the dimensions of the waveguide. The greater the relative permittivity s _r , the shorter the wavelength in the substrate ^substrate the smaller the dimensions of the waveguide.

[0041 ] For example, the input port 130 receives a first input waveform 101 (1 } having a first frequency fi . The Input waveform can be a voltage or current sinusoidal waveform with frequency of 5.8 ± 0.075 GHz. The waveguide 110 guides the first input waveform 101(1 ). from the input end 11 la to the opposing end 111 b thereof (e.g., along the z-axis), In this manner the antenna 100 or emits a first radiated wave 103(1 ) - having the first frequency f-i of the first input waveform 101(1 ) through the slots 118 of the waveguide 110. A first direction of propagation of the first radiated wave 103(1) is tilted by a first angle (90-OH), relative to the z~axis (in the y-z plane), that corresponds to the first frequency rY

[0042] As another example, the input port 130 receives a second input waveform 101(2) having a second frequency ¾. The waveguide 110 guides the second input waveform 101 (2) from the input end 111 a to the opposing end 111 b thereof, in this manner, a second radiated wave 103(2) having the second frequency f ₂ of the second input waveform 101(2) is output through the slots 118 of the waveguide 110. A second direction of propagation of the second wave 103(2) is tilted by a second angle (90-Q ₂ ), relative to the z-axis (in the y-z plane), that corresponds to the second frequency f2.

[0043] Referring now to FIG. I B, an antenna system 150 for wireless power transmission includes a plurality, here N ₂ , antennas 100(1 ) - 100(N ₂ ). The waveguides 110 of the N ₂ antennas 100(1 ) - 100(N ₂ ) of the antenna system 150 are parallel to each other (e.g., in the same x-z plane) and separated from each other by a distance δ. it should he appreciated that In this illustrative

embodiment, the waveguide Is provided by cascading identical elements on the x- z plane, along the z-directlon. The Input ports 130 of the N ₂ antennas 100 receive respective instances of the first input waveform 101 (f , ,) having the first frequency fi and phase φ,, where i=1. . . N2. The waveguides 110 of the N ₂ antennas 100 guide the respective instances of the first input waveform 101(fi,<pj) from the input end 111a to the opposing end 111 b thereof (e.g., along the z-axis). In this manner, a first radiated wave 103{fi) having the first frequency fi of the first input waveform is output through the slots 118 of the N ₂ waveguides 110, however, In this example, a first direction of propagation of the first radiated wave 103(fi) is tilted by the first angle (90-a-j), relative to the z~axis (in the y-z plane), that corresponds to the first frequency f-i, and by another angle (β , relative to the y-axis (in the x-y plane), that corresponds to the phases φ _{1 :} cp ₂ , <|>N2. [0044] Referring now to FIGs. 2Ά-2Ε in which like elements are provided having like reference designations throughout the several views, an antenna 200 for wireless power transmission, includes a waveguide 210 having input port 232. FIG. 2B is a top perspective view of opposing end 211 b of the waveguide 210 and FIG, 2C is a top perspective view of first end 21 la of the waveguide 210. FIG. 2D is a bottom perspective view of opposing end 21 l b of the waveguide 210 and FIG. 2E is a bottom perspective view of first end 211a of the waveguide 210.

[0045] The waveguide 210 has a bottom face 212 and a top face 214 (e.g., both parallel to the x-z plane), and side faces 216a _: 216b (e.g., both parallel to the y~z plane). In this example, the side faces 218a, 218b are conductive walls or plates. The waveguide 210 has a length L (e.g., L~310.8mm for N-i-12), width D (e.g., D ^~ 15.82mm), and thickness T (e.g., 1=0.782mm). The top face 214 has slots 218 separated from each other by a distance (e.g., each slot having a length si (e.g., Si=7.9mm) and a thickness t (e.g., t~1mm). The slots allow energy to be radiated in the form of electromagnetic waves,

[0048] Note that the bottom face 212 has no slots.

[0047] The waveguide 210 has partially transmissive barriers 220. Here, each barrier 220 is formed from two plates 240, arranged (e.g., in the x~y plane) orthogonally to respective side faces 218a, 218b, that are separated from each other by a distance S2 (e.g., S2~6.37mm).Aiternatively, each barrier 220 may be provided from a single plate .240, arranged (e.g., in the x-y plane) orthogonally to respective faces 218a, 216b, that has an aperture 242 of width s ₂ .

[0048] In one illustrative embodiment, the plate(s) 240 may be formed by plating cuts (that are, e.g., 4.7mm long along the x-axis and 0.5mm wide) in the dielectric material enclosed inside the conducting waveguide 210. A barrier 220 is separated from an adjacent slot 218 by a distance fe-0.28*!i. The conductive barriers may also be provided from plated through holes or provided in the substrate or one or more from conductive posts disposed in the waveguide (e.g. through a dielectric in a partially or fully dielectric loaded waveguide.) [0049]j Referring now to FIG. 3A, an antenna 300 for wireless power

transmission, includes a waveguide 310 having input port 332. FIG, 3B is a top perspective view of opposing end 31 l b of the waveguide 310 and FIG. 3C is a top perspective of first end 31 l a of the waveguide 310. FIG. 3D is a bottom

perspective view of opposing end 3 1 b of the waveguide 310 and FIG. 3E is a bottom perspective view of first end 31 l a of the waveguide 310. The waveguide 310 has a bottom face 312 and a top face 314 (e.g., both parallel to the x-z plane), and side faces (e.g., both parallel to the y-z plane), in this example, the first side face is a 1 D-array of conductive vias 316a, and the second side face is a 1 D-array of conductive vias 318b. Here, the vias of each of these 1 D-arrays have a diameter of about 0.5mm and are separated from each other by 1 .8mm. The waveguide 310 has a length L (e.g., L-310.8mm for width D (e.g.,

D=17.9mm measured between 1 D-array of conductive vias 316a and 1 D-array of conductive vias 316b) and thickness T (e.g., 7=0.762mm), The top face 314 has slots 318 separated from each other by a distance (e.g., h~.28.8mm}, each slot having a length Si (e.g., s "1 1.8mm) and a thickness f (e.g., t=0.9mm). Note that the bottom face 312 has no slots. The waveguide 310 has partially transmissive barriers 320. Here, each barrier 320 is formed from two conductive vias 340 having a diameter of about 0.5mm that are separated from each other by a distance Ss (e.g., s ₂ ~7.15mm}, Equivalency, each barrier 320 has an effective aperture 342 of width s ₂ formed by the two conductive vias 340. A barrier 320 is separated from an adjacent slot 318 by a distance l ₂ =0.03* . In embodiments, the cross-section of this waveguide can be trapezoidal. For example, the bottom face 312 can be larger than the top face 314 of the waveguide 310 shown in FIG. 3A - 3B.

[0050] In exemplary embodiments, a wireless power transmission system can include an additional input port coupled to the opposing end 1 1 1 b of the

waveguide 1 10. This additional input port can be configured to receive a second input waveform to be guided by the waveguide 1 10 from the opposing end 1 1 1 b to the first end 1 1 1 a. in embodiments, the second input waveform can have a different frequency than the first input waveform received at the input port coupled with the first end 1 1 1a. [0051] Referring now to FIG. 4A, a wireless power receiver in printed circuit form includes an array, here two, linearly polarized antennas 404a and 404b coupled through an RF transmission line to the receiver electronics 406 including an AC-to-DC converter and voltage stabilization circuitry, such as voltage multipliers, buck and/or boost regulators. In embodiments, the converter 408 converts the received oscillating electromagnetic energy (from the antennas 404a and 404b) to direct current for the use of a load or battery. The load or battery can be that of a mobile device or other electronic device.

[0052] In this illustrative embodiment, each of the antennas 404a, 404b are approximately 11.5 mm 408 by 15.5 mm 410 in dimension.

[0053] Referring now to FIG. 4Β _» a frequency selective surface (FSS) 412 for a wireless power receiver Is provided from a metamaterial that can include unit cells of conductor traces 414 with approximate size of 8,5 mm outer diameter and 4 mm Inner diameter with a top-center cut with width of 0.9 mm. As defined herein, a unit cell is the description of each slotted ring, which creates the periodic structure. The number of the unit cells are chosen to cover the area of the antennas 404a and 404b. The size of the unit cells are chosen based on the range of operating frequency. The traces of the unit ceils are shaped in a broken circle that function to increase the gain of the electromagnetic energy at the antennas and thereby increase power transfer efficiency at the chosen frequency for power transfer, in this case, 5.8 ± 0.075 GHz. In embodiments, the traces can be shaped in rectangular or other polygonal shapes.

[0054] In embodiments, the FSS 412 can increase efficiency by as much as 10%, 25%, 50%, or more. The substrate used can be standard PCB substrate or other low loss material. In embodiments, the dimensions and layout of the unit cells and antennas can scale with the substrate and operating frequency chosen for the system. For example, for a substrate materia! having a higher dielectric constant, the dimensions of the unit cells and/or antennas may be decreased. The range of commercial PCBs dielectric constants can span (but is not limited to) a range of about 3 to about 7. The higher the dielectric constant the smaller the unit cells dimensions. [0055] In another example, for higher operating frequencies, the dimensions of the unit cells and/or antennas may be decreased.

[0058] FIG. 4C shows a receiver system including the antenna board 402 and the FSS 412. The FSS 412 is positioned over the antenna 402 with a separation 418 of approximately 3 ~ 5 mm for operation in the s.s GHz range. In embodiments, the separation distance can depend on the point of antenna's maximum efficiency and gain.

[0057] A number of embodiments have been described. Nevertheless, it will be understood that various modifications may be made without departing from the spirit and scope of the disclosure.

[0058] For example, it has been recognized that many currently explored schemes for radiative wireless power transfer use either 2.4 GHz or 5.8 GHz frequencies. In order to transfer power over substantial distances with an acceptably low divergence angle (so that the efficiency would not be unacceptably low), the sources (transmitters) have to be fairly large. The divergence angle scales as D/A, where D is the linear size of the source, and Λ is the wavelength of the wave used to transmit the power. The size of the source scales as D ² , so the penalty for using low wavelength is quite steep. For a frequency of 5.8 GHz, the wavelength A is about 5 cm.

[0059] In contrast, schemes which propose to rely on ultra-sound for wireless power transfer, can have (for a given divergence angle) much smaller sources, simply because their wavelength is much smaller. For example, if fsouND-60 kHz, this corresponds to or 10x smaller than the electromagnetic (EM) wave scheme which uses f=5.8 GHz. So, the transmitters used by ultrasound schemes could in principle be l OOx smaller (in area) due to the smaller

wavelength. However, the technology for converting energy into ultrasound (and back) is much less mature compared to the EM counterparts.

[0080] it has thus also been recognized that the concepts system and techniques described herein may be used at higher frequencies (e.g. frequencies of about 30 GHz or about 80 GHz, or even higher). At 60 GHz, an EM wavelength will be about 0,5 cm, so one may capture many of the theoretical benefits of ultrasound (small wavelength). However, the technology to convert energy into EM waves at 30-60 GHz (and back) is much more mature. One reference on state-of-the-art of such conversion may be found at: http://repository.kuiib.kyoto u.ac. jp/dspace/bitstream/2433/179775/1/elex.10.20132009.pdf

[0061] Accordingly, other embodiments are within the scope of the following claims.