Technical Field

The present invention relates to a bi-directional DC-DC converter. Furthermore, the invention also relates to a system comprising at least two such bi-directional DC-DC converters.

Background

The developing trends of Isolated Bidirectional Direct Current-Direct Current (DC-DC) Converters (IBDC) are Wide Input - Wide Output (WIWO) voltage for very high efficiency, high power density and low cost. The resonant DC-DC converters are suitable technology to achieve high efficiency due to its intrinsic feature to achieve soft switching (Zero Voltage Switching, ZVS, and Zero Current Switching, ZCS). Furthermore, it is possible in these circuits to increase the switching frequency in order to reduce the size of the reactive components.

Common and widely used bidirectional DC-DC converters found in the industry today are the Dual Active Bridge (DAB) and resonant converters due to their availability to achieve high efficiency. However, there are still remaining drawbacks regarding the conventional resonant converters at bidirectional operation (i.e. forward- and reverse-mode), e.g. mainly the voltage gain characteristic at reverse mode of operation. Furthermore, the high AC-current at the low voltage side of the output filter resulting in high power losses and large volume of the filter if the current technology is going to be used.

With the described bidirectional topological circuits according to conventional solutions the current stress on the resonant components on the low voltage side is high and compromises the efficiency of the converter. Also, with the described bidirectional topological circuits according to conventional solutions it is not possible to achieve WIWO voltage and high efficiency. Moreover, it is very hard to get new topological circuits with reduced number of the active components (controlled semiconductors) where high reliability and performance in bidirectional energy conversion systems are required. Summary

An objective of the invention is to provide a concept which mitigates or solves the drawbacks and problems of conventional solutions. Another objective of the present invention is to provide improved bi-directional converters for WIWO voltage applications in power systems.

According to a first aspect of the present invention, the above mentioned and other objective is achieved with a bi-directional DC-DC converter comprising:

a first terminal circuit,

a second terminal circuit,

a transformer circuit,

a first high voltage side coupled to said first terminal circuit, and

a second low voltage side coupled to said second terminal circuit; wherein

said first high voltage side and said second low voltage side are coupled to each other by means of said transformer circuit, and

said first high voltage side comprises a resonant tank circuit coupled between a first bridge circuit of said first high voltage side and a high voltage side of said transformer circuit. The bridge circuits of the present converter may comprise active switches according to an implementation form of the first aspect.

With converters according to embodiments of the present invention very high variation of the input and output voltage, narrow frequency variation for voltage regulation, high efficiency, high power density and low cost can be achieved due the at least the following points. The present converter has simplified and more efficient layout due to the placement of the resonant tank on the high voltage side. This will also reduce the current stress and consequently the losses of the converter. Furthermore, no energy storage elements in the low voltage side of the converter are needed in order to get ZVS. Embodiments of the present invention can provide ZVS and ZCS in both directions of the converter.

Also, increased reliability is provided due to reduced number of the synchronous drivers for the low voltage side semiconductors but also due to the common reference that can be used. The internal energy consumption needed is also reduced with the present circuit layout which will increase the efficiency of the converters according to the present invention compared to conventional converters. According to a first implementation form of the first aspect as such, said resonant tank circuit comprises: a first branch comprising a first capacitance C _rl and a first inductance L _rl coupled in series with each other, a second capacitance C _r2 and a second inductance L _r2 ; wherein said first branch, said second inductance L _r2 and said second capacitance are coupled to a common node; wherein said second capacitance C _r2 is coupled between said common node and a first terminal of said high voltage side of said transformer circuit; wherein said second inductance L _r2 is coupled between said common node (C) and a second terminal of said high voltage side of said transformer circuit.

This can be denoted as a Capacitor-Inductor-Inductor-Capacitor (CLLC) type resonant tank. Therefore, reduced number of the active semiconductors at high voltage side and low voltage side are needed.

According to a second implementation form of the first implementation form of the first aspect,

a first terminal of the first capacitance C _rl forms a first (connection) terminal of said resonant tank circuit,

a second terminal of the first capacitance C _rl is connected to a first terminal of the first inductance L _rl ;

a second terminal of the first inductance L _rl is connected to a first terminal of the second capacitance C _r2 and to a first terminal of the second inductance L _r2 ;

a second terminal of the second inductance L _r2 forms a third (connection) terminal of said resonant tank circuit;

a second terminal of the second capacitance C _r2 forms a second (connection) terminal of said resonant tank circuit.

According to a third implementation form of the second implementation form of the first aspect,

said first terminal of said resonant tank circuit and said third terminal of said resonant tank circuit are connected to said first bridge circuit; and

said second terminal of said resonant tank circuit and said third terminal of said resonant tank circuit are connected to said high voltage side of said transformer circuit. According to a fourth implementation form of the first or second implementation forms of the first aspect, said first bridge circuit is a full bridge and said second low voltage side comprises a further full bridge coupled to a low voltage side of said transformer circuit, or said first bridge circuit is a half bridge, said second low voltage side comprises a push-pull circuit connected to the low voltage side of the transformer circuit and said transformer circuit comprises on its low voltage side a second winding comprising a center tap, or said first bridge circuit is a half bridge and said second low voltage side comprises a push-pull circuit with an autotransformer connected to the low voltage side of the transformer circuit. Hence, the present resonant tank can be added to any converter topology for different applications.

According to a fifth implementation form of the fourth implementation of the first aspect, said resonant tank circuit comprises: a first branch comprising a first capacitance C _rl and a first inductance L _rl coupled in series with each other, a second branch comprising a second inductance L _r2 , a second capacitance C _r2 coupled in series with each other, a third branch comprising a third capacitance C _r3 and a third inductance L _r3 coupled in series with each other; wherein said first branch, second branch and third branch are coupled to a common node (C); wherein said second branch is coupled between said common node and a first terminal of said high voltage side of said transformer circuit; and wherein said third branch is coupled between said common node and a second terminal of said high voltage side of said transformer circuit. This can be denoted as an Inductor-Capacitor-Inductor-Capacitor- Inductor-Capacitor or 3LC type resonant tank. Therefore, reduced number of the active semiconductors at high voltage side and low voltage side are needed. Further, the voltage gain characteristic is greater than 1 , only with passive components and boost and buck mode of operation is possible.

According to a sixth implementation form of the fifth implementation form of the first aspect, a first terminal of the first capacitance C _rl forms a first (connection) terminal of said resonant tank circuit;

a second terminal of the first capacitance C _rl is connected to a first terminal of the first inductance L _rl ;

a second terminal of the first inductance L _rl is connected to a first terminal of the second inductance L _r2 and to a first terminal of the third inductance L _r3 ;

a second terminal of the second inductance L _r2 is connected to a first terminal of the second capacitance C _r2 ; a second terminal of the second capacitance C _r2 forms a second (connection) terminal of said resonant tank circuit;

a second terminal of the third inductance L _r3 is connected to a first terminal of the third capacitance C _r3 ;

a second terminal of the third capacitance C _r3 forms a third (connection) terminal of said resonant tank circuit.

According to a seventh implementation form of the sixth implementation form of the first aspect,

said first (connection) terminal of said resonant tank circuit and said third (connection) terminal of said resonant tank circuit are connected to said first bridge circuit; and

said second (connection) terminal of said resonant tank circuit and said third (connection) terminal of said resonant tank circuit are connected to the high voltage side of said transformer.

According to an eighth implementation form of any of the fifth to seventh implementation forms of the first aspect, said first bridge circuit is a full bridge and said second low voltage side comprises a further full bridge coupled to a low voltage side of said transformer circuit, or said first bridge circuit is a half bridge and said second low voltage side comprises a full bridge coupled to a low voltage side of said transformer circuit, or said first bridge circuit is a half bridge, said second low voltage side comprises a push-pull circuit connected to the low voltage side of the transformer circuit and said transformer circuit comprises on its low voltage side a second winding comprising a center tap, or said first bridge circuit is a half bridge and said second low voltage side comprises a push-pull circuit with an autotransformer connected to the low voltage side of the transformer circuit Hence, the present resonant tank circuit can be added to any converter topology for different applications.

According to a ninth implementation form of any of the fifth to eight implementation forms of the first aspect, at least two of said first inductance L _rl , said second inductance L _r2 and said third inductance L _r3 are magnetically coupled to each other in one common magnetic core. Thereby, the number of components in the resonant tank circuit can be reduced.

According to a tenth implementation form of any of the implementation forms of the first aspect or the first aspect as such, a second filter is coupled between a positive and a negative terminal of the second terminal circuit. Thereby noise can be removed in the low voltage side of the converter. According to an eleventh implementation form of any of the implementation forms of the first aspect or the first aspect as such, a first filter is coupled in parallel with said first terminal and said first bridge circuit. Thereby noise can be removed in the high voltage side of the converter.

According to a second aspect of the invention, the above mentioned and other objective is achieved with a bi-directional DC-DC converter system comprising two or more bi-directional DC-DC converters according to the first aspect or any implementation form of the first aspect, wherein said two or more bi-directional DC-DC converters are interleaved with each other, i.e. the bi-directional DC-DC converters are coupled with each other in different configurations.

Interleaving is to operate two or more DC-DC converters in parallel and to operate the switches of the bridge circuits of each respective DC-DC converter with phase difference with respect to each other. Thereby, the resultant ripple current in the input and the output of the interleaved system can be minimized.

Interleaving two or more of the present converters is preferred for high power applications. Further, interleaving two or more converters reduces the number of capacitors needed for the output filter when phase-shifting control is used. It is also realized that the present converters can be interleaved in a variety of different serial and parallel configurations well known in the art. According to a first implementation form of the second aspect as such, said first high voltage sides of said two or more bi-directional DC-DC converters are coupled in series with each other.

According to a second implementation form of the first implementation form of the second aspect or the second aspect as such, said first high voltage sides of said two or more bidirectional DC-DC converters are coupled in parallel with each other.

According to a third implementation form of the first or second implementation forms of the second aspect or the second aspect as such, said second low voltage sides of said two or more bi-directional DC-DC converters are coupled in series with each other. According to a fourth implementation form of any of the first to third implementation forms of the second aspect or the second aspect as such, said second low voltage sides of said two or more bi-directional DC-DC converters are coupled in parallel with each other. A further aspect of the present invention relates to an electrical circuit comprising two or more coupling nodes (or terminals) for coupling to other electrical circuits and two or more inductances, wherein said two or more inductances are magnetically coupled to each other in one common magnetic core. Thereby, the number of inductive components in the electrical circuit and also the manufacturing costs are reduced.

It should be noted that further applications and advantages of the present converter and system will be apparent from the following detailed description.

Brief Description of the Drawings

The appended drawings are intended to clarify and explain different embodiments of the present invention, in which:

- Fig. 1 shows a bi-directional DC-DC converter according to an embodiment of the present invention;

- Fig. 2 shows a CLLC bi-directional DC-DC converter according to an embodiment of the present invention;

- Fig. 3a and 3b show voltage gain characteristics for forward and reverse modefor the CLLC bi-directional DC-DC converter as shown in Fig. 2;

- Figs. 4a-4c show other further CLLC bi-directional DC-DC converters according to embodiments of the present invention;

- Fig. 5 shows a 3LC bi-directional DC-DC converter according to an embodiment of the present invention;

- Figs. 6a and 6b show voltage gain characteristics for forward and reverse mode for the 3LC bi-directional DC-DC converter as shown in Fig. 5;

- Figs. 7a-7c show other further 3LC bi-directional DC-DC converter according to embodiments of the present invention;

- Fig. 8a and 8b show two different 3LC resonant tanks as they can be used with the embodiments shown in Figs. 5 and 7a-7c;

- Fig. 9 shows a bi-directional DC-DC converter system according to an embodiment of the present invention comprising CLLC bi-directional DC-DC converters; and

- Fig. 10 shows a bi-directional DC-DC converter system according to an embodiment of the present invention comprising 3LC bi-directional DC-DC converters. Detailed Description

Fig. 1 shows a simplified block diagram of a bi-directional DC-DC converter 100 according to an embodiment of the present invention. With reference to Fig. 1 the bi-directional DC-DC converter 100 comprises a (first) High Voltage (HV) (e.g. connection) terminal circuit 101 of an HV side 107, a (second) Low Voltage (LV) (e.g. connection) terminal circuit 103 of an LV side 109 and a transformer circuit 105. The HV side 107 is coupled to the first terminal circuit 101 of the DC-DC converter 100, and the LV side 109 is coupled to the second terminal circuit 103 of the DC-DC converter 100.

Further, the HV side 107 and the LV side 109 are coupled to each other by means of the mentioned transformer circuit 105. Moreover, the HV side 107 comprises a resonant tank circuit 1 1 1 coupled between a first bridge circuit 1 13 of the HV side 107 and a HV side of the transformer (circuit) 105. The terminal circuits 101 and 103 of the converter 100 and the different implementation form of this converter 100 described in the following typically comprise a positive terminal (for applying or providing a positive potential) and a negative terminal (e.g. for applying or providing a negative or GND potential). These positive and negative terminals are typically connection terminals adapted for connecting to one or more other devices. In the forward direction (High voltage in - Low voltage out) of the converter 100, the first terminal circuit 101 forms in input of the converter 100 and the second terminal circuit 103 forms an output of the converter 100. In the reverse direction (Low voltage in - High voltage out) of the converter 100, the second terminal circuit 103 forms in input of the converter 100 and the first terminal circuit 101 forms an output of the converter 100. HV side and LV side mean that at the HV side typically the comparatively highervoltages are applied/are provided when compared to the LV side.

According to an embodiment of the present invention, the resonant tank circuit 1 1 1 is of Capacitor-Inductor-Inductor-Capacitor (CLLC) type. Fig. 2 shows a bi-directional DC-DC converter 200 according to an embodiment of the present invention with a CLLC resonant tank 1 1 1. The bi-directional DC-DC converter 200 forms a possible implementation form of the bi-directional DC-DC converter 100 as shown in Fig. 1.

In the CLLC bi-directional DC-DC converter 200 an example of a CLLC resonant tank 1 1 1 implemented in the HV side 107 of the bi-directional DC-DC converter is shown in Fig. 2. Among the characteristics of this resonant tank circuit are the possibility to achieve WIWO voltage range in forward mode and acceptable voltage gain in reverse mode, but also high efficiency and high power density.

With reference to Fig. 2 the resonant tank circuit 1 1 1 according to the CLLC embodiment comprises a first capacitance C _rl , a first inductance L _rl , a second capacitance C _r2 , and a second inductance L _r2 .

A first terminal of the first capacitance C _rl forms a first (connection) terminal T1 of the CLLC resonant tank circuit 1 1 1 . A second terminal of the first capacitance C _rl is connected to a first terminal of the first inductance L _rl . A second terminal of the first inductance L _rl is connected to a first terminal of the second capacitance C _r2 and to a first terminal of the second inductance L _r2 . Further, a second terminal of the second inductance L _r2 forms a third (connection) terminal T3 of the resonant tank circuit 1 1 1 . A second terminal of the second capacitance C _r2 forms a (second) connection terminal T2 of the CLLC resonant tank circuit 1 1 1 .

Furthermore, the HV side 107 comprises a first full bridge circuit 1 13 coupled between the first HV terminal circuit 101 and the resonant tank circuit 1 1 1 . The first connection terminal T1 of the resonant tank circuit 1 1 1 is connected between third S3 and fourth S4 switches of the first bridge circuit 1 13. The third connection terminal T3 of the resonant tank circuit 1 1 1 is connected between first S1 and second S2 switches of the first bridge circuit 1 13. The second connection terminal T2 of the resonant tank circuit 1 1 1 is connected to a first terminal of the HV side (e.g. a first ending of a first winding) of the transformer circuit 105, and the third connection terminal T3 of the resonant tank circuit 1 1 1 is connected to a second terminal of the HV side (of a second ending of the first winding) of the transformer circuit 105.

In other words the CLLC resonant circuit 1 1 1 according to this embodiment comprises a first branch comprising a first capacitance C _rl and a first inductance L _rl coupled in series with each other, a second capacitance C _r2 and a second inductance L _r2 . The first branch, said second inductance L _r2 and said second capacitance are coupled to a common node C. Said second capacitance C _r2 is coupled between said common node C and the first terminal of said high voltage side of said transformer circuit 105. Said second inductance L _r2 is coupled between said common node C and the second terminal of said high voltage side of said transformer circuit 105. The values for the different capacitances and inductances of the present resonant tank 1 1 1 are dependent on the particular application. The HV side 107 includes the first terminal circuit 101 which is connected to first and second terminals of a first filter 1 17 implemented as a capacitance C _HV in this particular example. In detail, the first filter 1 17 is connected between the positive terminal and the negative terminal of the first terminal circuit 101 . The first and second terminals of the first filter 1 17 are in turn connected to a positive terminal and a negative terminal of the full bridge circuit 1 13, respectively. The full bridge circuit 1 13 comprises switches S1 , S2, S3 and S4 implemented as N-Channel Mosfet transistors in this example. However, other implementations for the switches are possible too (such as Insulated Gate Bipolar Transistor, IGBT; Metal Oxide Silicon Field Effect Transistor, MOSFET; Junction Gate Field-Effect Transistor, JFET; Gate Turn-off Thyristor, GTO).

Mentioned switches S1 , S2, S3 and S4 of the full bridge circuit 1 13 of the HV side are followed by the above described CLLC resonant tank circuit 1 1 1 which in turn is connected to the HV side of the transformer circuit 105. The transformer circuit 105 magnetically couples the HV side 107 and the LV side 109 of the converter device 200.

Further, first and second terminals of the LV side (e.g. endings of a second winding) of the transformer (circuit) 105 are connected to a second full bridge circuit 1 15 of the LV side 109. The second full bridge circuit 1 15 includes first Sr-ι _, second Sr _2, third Sr ₃ and fourth Sr ₄ switches. A positive and a negative connection terminals of the second full bridge circuit 1 15 are connected to first and second terminals of a second filter 1 19 of the LV side 109 which in this example is implemented as a capacitance C _LV . Finally, the first and second terminals of the second filter 1 19 are connected to the second terminal circuit 103 of the present DC-DC converter 200. In detail, the first filter 1 17 is connected between the positive terminal and the negative terminal of the second terminal circuit 103.

The voltage gain characteristics for both forward (shown in Fig. 3a) and reverse mode (shown in Fig. 3b) of this particular embodiment in Fig. 2 are shown in Fig. 3a and 3b. The y-axis represents the voltage and the x-axis represents the frequency. As it can be seen in the graphs of Fig. 3a and 3b, the natural resonance frequency of the resonant tank is equal in both directions. In the reverse mode, the voltage gain characteristic is limited and highly dependent of the quality factor Q which is dependent on the values of the components in the resonant tank circuit 1 1 1 (in the Fig. 3a and 3b Q = 10, 2 and 0.1 are shown). However, this is a design related issue and will depend of the choice of the values for the components (parameters) of the resonant tank and the application.

Based on the configuration of the LV side 107 of the above described converter, different topological implementation forms of the bi-directional DC-DC converter are possible which are illustrated in Fig. 4a-4c. These implementation forms relate to the configurations of the first bridge circuit 1 13 and the second bridge circuit 105, respectively.

In the converter 210 shown in Fig. 4a, the first bridge circuit 1 13 in the HV-side 107 is implemented as a Half Bridge (HB) circuit and the second bridge circuit 1 15 in the LV side 109 is implemented as a Full Bridge (FB) circuit. The HB circuit 1 13 in the HV side 107 in Fig. 4a comprises first S1 and second S2 switches; first CB1 and second CB2 capacitances (CB1 and CB2 may be part of the resonant tank circuit in certain applications when the first bridge circuit has this HB configuration); and first Del and second Dc2 clamping diodes. The first connection terminal T1 of the resonant tank circuit 1 1 1 is connected between a series connection of the first capacitance CB1 in parallel with the first clamping diode Del and the second capacitance CB2 in parallel with the second clamping diode Dc2. The third connection terminal T3 of the resonant tank circuit 1 1 1 is connected between the series connection of the first switch S1 and the second switch S2.

The FB circuit in the LV side 109 in Fig. 4a is configured in the same way as the FB circuit in Fig. 2 as described above.

In the converter 220 as shown in Fig. 4b, the first bridge circuit 1 13 in the HV-side 107 is implemented as a Half Bridge circuit (as the one in Fig. 4a). Furthermore, the LV side 107 of the convert 220 comprises instead of a bridge circuit a push pull - autotransformer circuit 1 16.

The PP - autotransformer circuit 1 16 in the LV side in Fig, 4b comprises switches Sr1 , Sr2 and an autotransformer 123. The autotransformer 123 has two windings (first and second windings) in one common core. The first winding is connected the first switch Sr1 , and the second winding is connected to the second switch Sr2. The midpoint of the autotransformer 123 is connected to a positive terminal of the LV side. The common point of Sr1 and Sr2 are connected to a negative terminal of the LV side. Further, the first terminal of the LV side (e.g. a first ending of a second winding) of the transformer 105 is connected between the first winding of the autotransformer 123 and the first switch Sr1 . The second terminal of the LV side (e.g. a second ending of the second winding) of the transformer 105 is connected between the second winding of the autotransformer 123 and the second switch Sr2.

In the converter 230 shown in Fig. 4c, the first bridge circuit 1 13 is implemented as HB circuit. Furthermore, the converter 230 comprises in its LV side instead of a bridge circuit a Push Pull (PP) Circuit 1 18. The PP circuit 1 18 comprises a first switch Sr1 and a second switch Sr2. In the embodiment shown in Fig. 4c, the first switch Sr1 and the second switch Sr2 are implemented exemplarily as N-channel Mosfets. The transformer circuit 105 is implemented as a transformer comprising on its HV side a first winding connected with its first end to the second terminal T2 and its second end to the third terminal T3 of the resonant tank circuit 1 1 1 . Furthermore, on LV side the transformer comprises a second winding having a first end, a center tap and a second end. A first terminal of the first switch Sr1 (e.g. a drain terminal) is connected to the second end of the second winding. A first terminal of the second switch Sr2 (e.g. a drain terminal) is connected to the first end of the second winding. Second terminals (e.g. source terminals) of the first switch Sr1 and second switch Sr2 are connected together to a negative terminal of the second terminal circuit 103. Furthermore, the center tap of the transformer is connected to the positive terminal of the second terminal circuit 103. A second filter 0_v is connected between the negative and positive terminal of the second terminal circuit 103.

According to an embodiment of the present invention, the tank circuit 1 1 1 is of three Inductor-Capacitor type, i.e. Inductor-Capacitor-Inductor-Capacitor-Inductor-Capacitor, denoted 3LC in this disclosure. Fig. 5 shows such a 3LC resonant tank 1 1 1 implemented in the HV side 107 of a bi-directional DC-DC converter 300 according to an embodiment of the to the present invention, which forms a possible implementation form of the converter 100. Among the characteristics of this resonant tank circuit 1 1 1 are the possibility to achieve suitable voltage gain in reverse mode, but also high efficiency and high power density. Another important effect is that the WIWO voltage range can be achieved with a very narrow frequency variation.

From left in Fig. 5 the HV side 107 includes a first terminal circuit 101 of the HV side which is connected to first and second terminals of a first filter 1 17 implemented as a capacitance in this example, C _HV . The first and second terminals of first filter 1 17 are in turn connected to a positive terminal and a negative terminal of the FB circuit 1 13 as described above. Mentioned switches S1 , S2, S3 and S4 of the FB circuit 1 13 of the HV side are followed by the 3LC resonant tank circuit 1 1 1 . The FB circuit is coupled to connection terminals T1 and T3 of the resonant tank circuit 1 1 1 . Further, the resonant tank circuit 1 1 1 is connected to the LV side of the transformer circuit 105 via connection terminals T2 and T3. The transformer circuit 105 magnetically couples the HV side 107 and the LV side 109 of the present converter 300.

In the example shown in Fig. 5, the LV side 109 of the converter 300 is implemented as a push pull circuit 1 18 (comprising switches Sr-ι , Sr ₂ in combination with the transformer circuit 105 having the second winding with center tap (as shown in Fig. 4c). Hence, the converter 300 differs from the converter 230 in that the resonant tank circuit 1 1 1 in the converter 300 is implemented as 3LC resonant tank.

Alternatively also an implementation with a push pull-autotransformer circuit 1 16 on the LV side 109 would be possible (as shown in Fig 4b).

Fig. 8a shows one proposed 3LC resonant tank 1 1 1 configuration for use in embodiments of the present invention which comprises a first capacitance C _rl , a first inductance L _rl , a second inductance L _r2 , a second capacitance C _r2 , a third inductance L _r3 and a third capacitance C _r3 . A first terminal of the first capacitance C _rl forms a first connection terminal T1 of the 3LC resonant tank circuit 1 1 1 . A second terminal of the first capacitance C _rl is connected to a first terminal of the first inductance L _rl . A second terminal of the first inductance L _rl is connected to a first terminal of the second inductance L _r2 and to a first terminal of the third inductance L _r3 . A second terminal of the second inductance L _r2 is connected to a first terminal of the second capacitance C _r2 . A second terminal of the second capacitance C _r2 forms a second connection terminal T2 of the resonant tank circuit 1 1 1 . A second terminal of the third inductance L _r3 is connected to a first terminal of the third capacitance C _r3 . A second terminal of the third capacitance C _r3 forms a third connection terminal T3 of the resonant tank circuit 1 1 1 . As can be seen from Fig. 8a, the three inductances L _rl , L _r2 , L _r3 are all connected to a common node C.

In other words the proposed 3LC resonant tank configuration shown in Fig. 8a comprises a first branch comprising a first capacitance C _rl and a first inductance L _rl coupled in series with each other, a second branch comprising a second inductance L _r2 , a second capacitance C _r2 , a third branch comprising a third capacitance C _r3 and a third inductance L _r3 coupled in series with each other. The first branch is coupled in series with the second branch, and the third branch is coupled between a common node C of the first branch and the second branch and the third terminal T3 of the resonant tank circuit 1 1 1 . The second T2 and the third terminals T3 of the resonant tank circuit 1 1 1 are to be coupled to the high voltage side of the transformer circuit 105. The values for the different capacitances and inductances of the present resonant tank 1 1 1 are dependent on the particular application.

The features of this resonant tank 1 1 1 are unique as it increases the voltage gain for both directions to be greater than 1 which is the gain obtained at the resonant frequency. This feature makes it possible to achieve WIWO voltage variation. The voltage gain characteristics for both forward and reverse mode are shown in Fig. 6a (forward mode) and 6b (reverse mode) for the 3LC bi-directional DC-DC converter 300 as shown in Fig. 5. The y-axis represents the voltage and the x-axis represents the frequency. As it can be seen in the graphs in Fig. 6a and 6b, the natural resonance frequency of the tank is equal in both directions. The effect introduced by the parallel LC-network (L _r3 and C _r3 ) makes the gain to change from 0 to infinity in a very sharp way. The final value is depending of the quality factor Q (Q = 10, 2, 0.1 are shown in Fig. 6a and 6b). This result in high gain, but it is also important to mention that the characteristics of this converter are the same as the standard LLC resonant tank for both directions. This guarantees that the converter will always work in the most optimum power transferring point h both forward and reverse modes.

In Fig. 8b a magnetic integration of the first L _rl and the second L _r2 inductances of the resonant tank circuit 1 1 1 using the same magnet core is illustrated. This simplifies the building of the 3LC resonant tank circuit 1 1 1 of the present converter and also reduces the number of components. However, all the inductors of the resonant tank circuit 1 1 1 could be integrated in a single magnetic component. Therefore, embodiments of the present invention also relate to an electrical circuit 1 1 1 comprising two or more coupling nodes for coupling to other electrical circuits and two or more inductances, wherein the two or more inductances are magnetically coupled to each other in one common magnetic core. The present electrical circuit 1 1 1 can also be used in other applications in which two or more inductances are used.

Based on the 3LC resonant tank 1 1 1 , we have different converter topological circuits that are illustrated (additionally to the one shown in Fig. 5) in Fig. 7a-7c according to further embodiments of the present invention.

The FB, H B and PP circuits in Fig. 7a-7c are configured in the same way as the FB, H B and PP circuits in the embodiments shown in Fig. 2, 4a, 4b. Fig. 7a shows a Full Bridge - Full Bridge implementation for the bridge circuits 1 13, 1 15 as the one in Fig. 2. Fig. 7b shows a Half Bridge - Full Bridge implementation for the bridge circuits 1 13, 1 15 as the one shown in Fig. 4a. Fig. 7c shows a Half Bridge - Push Pull circuit with Autotransformer implementation for the bridge circuit 1 13 and LV side 109 as the one shown in Fig. 4b.

For high power applications, interleaving two or more DC-DC converters of embodiments of the present invention is preferred so as to obtain a bi-directional DC-DC converter system.

For instance, one possible configuration is to have series connection of the HV sides 107a, 107b,..., 107n of the DC-DC converters and parallel connection of the LV sides 109a, 109b, 109n of the DC-DC converters. This configuration setup is illustrated in the systems in Fig. 9 and 10, respectively. The single DC-DC converter can be of any type according to embodiments of the present invention. Other configurations for the connection of the individual converters the system 1000 are: in parallel in the HV side 107 and in series in the LV side 109, in series in the HV side 107 and in series in the LV side 109, and in parallel in the HV side 107 and in parallel in the LV side 109. Fig. 9 shows a DC-DC converter system 900 according to an embodiment of the present invention in which the resonant tank circuit 1 1 1 of each DC-DC converter in the system 900 is of the CLLC type as explained above. In detail does Fig. 9 show an interleaving of a plurality of converters 200 as shown in Fig 2. In this system 900, the HV sides 107a...107n of the converters are connected in series between a positive HV terminal and a negative HV terminal of the system 900. The LV sides 109a...109n of the converters are connected in parallel to a positive LV terminal and a negative LV terminal of the system 900.

Fig. 10 shows a DC-DC converter system 1000 according to an embodiment of the present invention in which the resonant tank circuit 1 1 1 of each converter in the system 1000 is of the 3LC type as explained above. In details does Fig. 10 show an interleaving of a plurality of converters 300 as shown in Fig. 5. In this system 1000, the HV sides 107a...107n of the converters are connected in series between a positive HV terminal and a negative HV terminal of the system 1000. The LV sides 109a...109n of the converters are connected in parallel to a positive LV terminal and a negative LV terminal of the system 1000. Although the examples in Figs. 9 and 10 showed an interleaving of the DC-DC converters 200 and 300, further embodiments also include an interleaving the other DC-DC converters introduced in this documents (also in the general form of the DC-DC converter 100). Finally, it should be understood that the present invention is not limited to the embodiments described above, but also relates to and incorporates all embodiments within the scope of the appended independent claims.