This Application claims the benefit of priority to U. S. Patent Application No. 15/433,862, filed February 15, 2017, which claims priority to PCT

Application No. PCT/CN2017/070608, filed January 9, 2017, which are hereby incorporated by refrence in their entirety.

FIELD OF TH E DISCLOSURE

This document relates generally to interface circuits for electronic sensors. Some embodiments relate to test circuits for electronic sensors.

BACKGROUND

Smart sensors are electronic circuits that measure some aspect of their environment and trigger computing resources to perform predefined functions in response to the measurements. Smart sensors are useful in application such as implementing an internet of things (loT). Sometimes the output of a smart sensor needs to be tailored to the monitoring electronics operatively coupled to the smart sensors to acquire information for the computing resources. The present inventors have recognized a need for improved interface circuits for smart sensor circuits.

SUMMARY OF THE DISCLOSURE

This document relates generally to interface circuits for electronic sensors.

Aspect 1 of the present disclosure includes subject matter (such as a test circuit for an electronic sensor) comprising a load resistance connectable in series with the electronic sensor to form a seri es resistance of the load resistance and the internal impedance of the electronic sensor; an excitation circuit configured to apply a predetermined voltage to a circuit element; and a measurement circuit configured to: initiate applying the predetermined voltage to the series resistance and determining the series resistance: initiate applying the predetermined voltage to the load resistance and determining the load resistance; and calculate the internal impedance of the sensor usin the determined series resistance and the load resistance, and provide the calculated internal impedance to a user o process.

In aspect 2, the subject matter of aspect 1 optionally includes an excitation circuit configured to apply a specified electrical signal having a signal amplitude less than twenty millivolts (20mV) to the series resistance, and the internal impedance of the electronic sensor is less than ten ohms (10Ω).

In aspect 3, the subject matter of one or both of Aspects 1 and 2 optionally include the electronic sensor being an electro-chemical sensor.

Aspect 4 includes subject matter (such as an integrated circuit), or can optionally be combined with the any combination of Aspects 1-3 to include such subject matter, comprising an excitation circuit configured to apply excitation signals to a sensor circuit, wherein the excitation circuit includes a configurable first circuit gain stage and a configurable second circuit gain stage, wherein in a first gain mode the excitation circuit generates a first excitation signal from a test signal using a first signal gain applied by the first circuit gain stage and a second signal gain applied by the second circuit gain stage, and in a second gain mode the excitation circuit generates a second excitation signal from the test signal using a third signal gain applied by the first circuit gain stage and a fourth signal gain applied by the second circuit gain stage; and a measurement circuit configured to selectively initiate application of the first excitation signal or the second excitation signal to the electronic sensor and calculate the internal impedance of the sensor

In aspect 5, the subject matter of Aspect 4 optionally includes a measurement circuit configured to initiate application of the first excitation signal to the electronic sensor when the internal impedance of the sensor has a first internal impedance range and initiate application of the second excitation signal to the electronic sensor when the internal impedance of the sensor has a second internal impedance range, wherein the first internal impedance is greater than the second internal impedance range.

In aspect 6, the subject matter of one or both of Aspects 4 and 5 optionally includes the signal gain of the second gain circuit stage being one in the first gain mode, and less than one and greater than zero in the second gain mode.

In aspect 7, the subject matter of one or any combination of Aspects 4-6 optionally includes the signal gain of the first gain circuit stage being greater than one in the first gain mode, and less than one and greater than zero in the second gain mode.

In aspect 8, the subject matter of one or any combination of Aspects 4-7 optionally includes a digital-to-analog converter (DAC) circuit configured to generate the test signal.

Aspect 9 includes subject matter (such as a test circuit), or can optionally be combined with one or any combination of Aspects 1 -8 to include such subject matter, comprising: an adjustable bridge resistance and a calibration resistance for coupling to an electronic sensor; an excitation circuit configured to apply an excitation signal to the electronic sensor, bridge resistance and calibration resistance; and a measurement circuit configured to: apply a first excitation signal to a calibration resistance and measure a calibration current; apply the first excitation signal to a first bridge resistance and measure a first bridge current; apply a second excitation signal to the first bridge resistance and measure a second bridge current; apply the second excitation signal to the sensor and measure a sensor current; and calculate the internal impedance of the sensor using the calibration resistance, the calibration current, the first bridge current, the second bridge current, and the sensor current.

In aspect 10, the subject matter of Example 9 optionally includes a multiplexer circuit configured to selectively apply an excitation signal to the calibration resistance, the adjustable bridge resistance, or the sensor.

In aspect 1 1, the subject matter of one or both of Aspects 9 and 10 optionally includes a multiplexer circuit configured to apply an excitation signal to the calibration resistance, and the measurement circuit is configured to calculate the calibration resistance using the excitation signal.

In aspect 12, the subject matter of one or any combination of Aspects 9-

11 optionally includes a measurement circuit configured to set the bridge resistance to a coarse bridge resistance value prior to the applyin the excitation signal to the bridge resistance. In aspect 13, the subject matter of one or any combination of Aspects 9- 12 optionally includes a measurement circuit configured to: apply a third excitation signal to the first bridge resistance and measure a third bridge current, apply the third excitation signal to a second bridge resistance and measure a fourth bridge current, and calculate the internal impedance of the sensor using the calibration resistance, the calibration current, the first bridge current, the second bridge current, the third bridge current, the fourth bridge current, and the sensor current.

In aspect 14, the subject matter of one or any combination of Aspects 9- 13 optionally includes the electronic sensor being an electrochemical sensor and the resistance of the electronic sensor is representative of the remaining useful life of the electrochemical sensor.

Aspect 15 includes subject matter (such as an apparatus), or can optionally be combined with the subject matter of one or any combination of Examples 1 - 1 4 to include such subject matter comprising an integrated circuit. The integrated circuit incl udes an input to receive an electrical signal from an electronic sensor, wherein the electrical signal includes a direct current (DC) offset and a varying signal component; a digital-to-analog converter (DAC) circuit configured to subtract the DC offset from the input signal; a

programmable gain amplifier (PGA) operatively coupled to the DAC circuit, wherein the PGA ci rcuit is configured to apply signal gain to the varying signal component of the input signal; and a measurement circuit configured to generate a measure of the varying signal component.

In aspect 16, the subject matter of Aspect 15 optionally includes a measurement circuit that incl udes an analog-to-digital converter (ADC) circuit configured to generate a measure of the varying signal component.

In aspect 17, the subject matter of one or both of Aspects 15 and 16 optionally includes a measurement circuit including a fast Fourier transform ( FFT) circuit configured to measure a frequency response of the varying signal component.

In aspect 18, the subject matter of one or any combination of Aspects 15- 17 optionally includes an electronic sensor operatively coupled to the integrated circuit, wherein the electronic sensor is a resistive electronic sensor. In aspect 19, the subject matter of one or any combination of Aspects 15- 18 optionally includes an electronic sensor being a gas sensor and the electrical signal from the electronic sensor is proportional to an amount of gas in an atmosphere.

In aspect 20, the subject matter of one or any combination of Aspects 15- 20 optionally includes a detection circuit, wherein the electronic sensor is an oxygen sensor and the detection circuit is configured to generate an indication of a lower explosive limit according to the measure of the var in signal component.

Aspect 2 1 can include, or can optionally be combined with any portion or combination of any portions of any one or more of Examples 1-20 to include, subject matter that can include means for performing any one or more of [he functions of Aspects 1-20, or a machine-readable medium including instructions that, when performed by a machine, cause the machine to perform any one or more of the functions of Aspects 1-20.

These non-limiting aspects can be combined in any permutation or combination. This section is intended to provide an overview of subject matter of the present patent application. It is not intended to provide an exclusive or exhaustive explanation of the invention. The detailed description is included to provide further information about the present patent application.

BRIEF DESCRIPTION OF THE DRAWINGS

In the drawings, which are not necessarily drawn to scale, like numerals may describe similar components in di fferent views. Like numerals havin different letter suffixes may represent different instances of similar components. The drawings illustrate generally, by way of example, but not by way of limitation, various embodiments discussed in the present document.

FIGS. 1 A and IB are block diagrams representing a test circuit and sensor circuit.

FIGS. 2 A and 2B are block diagrams representing another test circuit 204 electrically coupled to a sensor circuit.

FIG. 3 is a flow diagram of an example of a method of controlling a test circuit to measure an internal impedance of an electronic sensor. FIG. 4 is circuit diagram of portions of another example of a test circuit electrically coupled to a sensor circuit.

FIG. 5 is a flow diagram of another example of a method of controlling a test circuit to measure an internal impedance of an electronic sensor.

FIG. 6 is circuit diagram of portions of another example of a test circuit electrically coupled to a sensor circuit.

FIG. 7 is a flow diagram of an example of a method of controlling a test circuit to measure an internal i mpedance of an electronic sensor.

FIG. 8 is a circuit diagram of portions of another example of a test circuit electrically coupled to a sensor ci rcuit.

FIG. 9 is an example of the output of a sensor circuit.

FIG. 10 is a flow diagram of an example of a method of controlling a test circuit to measure an internal impedance of an electronic sensor. DETAILED DESCRIPTION

Some smart sensor circuits can include electro-chemical sensors to monitor an amount or concentration of gas. System demands on the sensors often require a sensor circuit to have low power consumption and exhibit low noise to reduce errors. To maximize longevity and minimize servicing, it is desired for the monitoring circuits to also have low power consumption. This can provide challenges in designing circuits to monitor different types of smart sensor circuits. For instance, it may be necessan. to measure the impedance of a sensor circuit for diagnostic purposes, but smart sensors can have a wide range of internal impedances. Some sensor may have an internal resistance greater than ten kilo-ohms ( l kiT) while other sensors may have a low internal resistance (e.g., 1 Ω). A sensor with a low internal i mpedance typically requires a higher voltage measurement signal to provide an adequate signal to noise ratio (SNR). However, applying a higher voltage measurement signal to a low impedance can lead to high current consumption by the measurement circuit and sometimes the sensor circuit cannot tolerate the currents associated with the higher measurement.

FIGS. 1 A and I B are block diagrams of a test circuit 104 and sensor circuit 106. The test circuit 104 may be included on an integrated circuit. To measure the internal impedance of the sensor circuit, an excitation signal is applied between a drive or "D" connection and a transinipedance amplifier (TIA) or "T" connection. The "P" and "N" connections are sensing nodes for operation of the sensor. To determine the internal impedance of the sensor circuit, the test circuit applies an excitation signal to the sensor circuit using the D and T connections. I n FIG. I A the excitation signal has a magnitude of fifteen millivolts (15mV), and the sensor circuit 106 has an internal impedance of 181Ω. Applyin the excitation signal results in a current through the sensor of

0.08milliamps (0.08mA). The test circuit can determine the internal resistance of the sensor circuit using Ohm's Law. The test circuit can provide the determined internal i mpedance to a user ( e.g.. by presenting the value of on a display ) or to a process ( e.g.. a process that stores the value in memory or a process that uses the determined impedance to take some action ).

In FIG. IB, the sensor circuit 106 has an internal resistance of I Ω. but it may be desired to measure the sensor with the same 15mV excitation signal. However, a straightforw ard application of the excitation signal results in a current of 15mA. This current may cause problems for multiple reasons. For instance, the current may be too large for a desired power consumption, or the sensor circuit may not be able to tolerate a current of that magnitude. Also, try ing to accommodate a current of 0.08mA and a current of 15mA may cause accuracy issues in measurements made by the monitoring circuits. Reducing the excitation voltage may signi ficantly reduce the SNR.

FIGS. 2 A and 2B are block diagrams of further examples of a test circuit 204 el ectrically coupled to a sensor circuit 206. The test ci rcui t can be used to determine internal impedances of sensor circuits of about 200Ω and also sensor circuits with internal i mpedances less than 10Ω. The test circuit incl udes a load resistance Rioad, an excitation circui t 208, and a measurement circuit 210. The load resistance may have a resistance value of Ι00Ω (in certain embodiments the load resistance has a resistance value of about 200 Ω). The measurement circuit can include logic circuits to perform the described functions. I n variations, the measurement circuit includes a processor such as a microprocessor. I n FI G. 2 A. when a sensor circuit with a low i mpedance is to be monitored, the measurement circuit 2 10 connects the load resistance in series with the internal i mpedance of the sensor circuit to form a series resistance. The excitation circuit 208 applies an excitation signal having a predetermi ned voltage to the series resistance. In variations the predetermined voltage is less than or equal to 20mV. The measurement circuit determines the series resistance using the resulting current and predetermined voltage. In FIG. 2B, the test circuit then applies the excitation signal to just the load resistance. The excitation signal determines the load resistance using the resulting current and predetermined voltage. The test circuit determines the internal impedance of the sensor circuit by subtracting the load resistance from the series resistance.

Adding in the load resistance results in an internal impedance that is comparable between the two types of sensors. This improves the accuracy in the values of impedance determined by the test circuit. In some examples, the measurement circuit calibrates the predetermined voltage of the excitation signal. A calibration resistor of a predetermined resistor can be electrically connected to outputs of the test circuit and the test circuit can adjust the excitation signal until a specified current is measured correspondin to the predetermined voltage of the excitation signal.

FIG. 3 is a flow diagram of an example of a method 300 of controlling a test circuit to measure an internal impedance of an electronic sensor. At 305, a load resistance is electrically connected in series with the sensor to form a series resistance of the load resistance and the internal impedance of [he sensor. At 310, an excitation signal with a predetermined voltage is applied to the series resistance and determining the series resistance is determined (e.g., by Ohm's Law). At 315, the predetermined voltage is applied to the load resistance and the load resistance is determined. At 320, the internal impedance of the sensor is determined using the determined load resistance and series resistance. A value of the internal impedance is provided to a user or process. The approach can be used for other ranges of internal impedance. For example, the test circuit can be used to measure sensor internal impedances of about IkQ to 1Ω.

FIG. 4 is circuit diagram of portions of an example of a test circuit 404 electrically coupled to a resistor (Rx) representing the internal impedance of a sensor circuit 406. The test circuit 404 may be included on an integrated circuit. The test circuit 404 includes a digital to analog converter (DAC) circuit 412, an excitation circuit 414 and a measurement circuit 416. To measure the internal impedance, a test signal is generated using a digital to analog converter DAC circuit 412. Using excitation operational amplifier 424, the excitation circuit 414 applies an excitation circuit generated using the test signal to the sensor circuit. A monitoring signal resulting from the excitation is used by the measurement circuit 416 to determine the internal impedance. For instance, an excitation signal of a predetermined voltage can be applied to the sensor circuit and the resulting current signal can be used to determine the internal impedance. The DAC circuit 412 allows excitation signals of different frequency and magnitude to be generated, such as by controlling the DAC circuit 412 with a processor or other control circuit (e.g., a waveform generator).

When the internal impedance to be measured is low, the voltage of the excitation signal may need to be reduced to limit the current through the sensor and limit the power consumption of the test. A challenge with measuring internal impedances for different types of sensors with very different internal impedances is that circuit noi se can become significant as the voltage of the excitation signal is reduced.

The excitation circuit 414 includes a configurable first circuit gain stage

420 and a configurable second circuit gain stage 41 8. The first circuit gain stage 420 includes a programmable gain amplifier (PGA). The second circuit gain stage includes resistors Rd and cross coupled switch circuit 422. The gain of the first circuit stage is configurable by changing the programmable gain and the gain of the second circuit gain stage 418 is configurable by changing the state of the cross coupled switch circuit 422. The combined signal gain of the excitation circuit 414 is configured by the measurement circuit (e.g., using a control circuit) according to whether the internal impedance of the sensor circuit to be measured is in a higher impedance range or lower impedance range. A higher signal gain is provided when the internal impedance is in the higher impedance range.

When the sensor circuit has a value of internal impedance in the higher range, the excitation circuit 414 is configured in a first gain mode. The excitation circuit generates a first excitation signal from the DAC circuit test signal usin a first signal gain applied by the first circuit gain stage and a second signal gain applied by the second circuit gain stage. In an example not intended to be limiting, the gain of the first circuit gain stage 420 is 1 and the gain of the second circuit gain stage 418 is two to provide an overall signal gain of two to the test signal in the first gain mode. When the sensor circuit has a value of internal impedance in the lower range, the excitation circuit 414 is configured in a second gain mode. The excitation circuit generates a second excitation signal from the DAC circuit test signal using a third signal gain applied by the first circuit gain stage and a fourth signal gain applied by the second circuit gain stage. The gains in the second gain mode can be gain values between zero and one. In an example, the gain of the first circuit gain stage 420 is one-tenth (1/10) and the gain of the second circuit gain stage 418 is one-half (½) to provide an overall signal gain of one- twentieth (1/20) to the test signal in the second gain mode. The values of signal gain provided by the second gain mode can be changed by changing the resistance values. In certain examples, the second gain stage provides a gain of four or five in the first gain mode and one-fourth (1/4) or one-fifth (1/5) in the second gain mode. The measurement circuit 416 selectively initiates application of the first excitation signal or the second excitation signal to the electronic sensor and calculate the internal impedance of the sensor. The small signal gain when the internal impedance is in the lower range reduces circuit noise of the PGA and excitation operational amplifier 424. This improves accuracy in the internal impedance measurement in the lower range.

FIG. 5 is a flow diagram of an example of a method 500 of controlling a test circuit to measure an internal impedance of an electronic sensor. At 505, a first excitation signal in a first gain mode is applied to the sensor when the internal impedance of the sensor has a first internal impedance range. In the first gain mode, the first excitation signal is generated from a test signal using a first signal gain generated using a first circuit gain stage and a second signal gain generated using a second circuit gain stage.

At 510, a second excitation signal in a second gain mode is applied to the sensor when the internal impedance of the sensor has a second internal impedance range. In some examples, the values of impedance in the second impedance range are lower than the value of impedance in the first impedance range. In the second gain mode, the second excitation signal is generated from the test signal using a third signal gain using the first circuit gain stage and a fourth signal gain using the second signal gain stage.

At 515, the internal impedance of the sensor is calculated using the first excitation signal when in the first gain mode and using the second excitation signal when in the second gain mode. The calculated internal impedance can be provided to a user or process. The internal impedance range of the sensor circuit and consequently which signal gain to use in measuring the sensor circuit may be known ahead of time (e.g., by the type of sensor) and programmed by a user. In other examples, the measurement circuit can determine which signal gain to apply to the excitation circuit. In some examples, the sensor circuit includes an identifier (e.g., a machine-readable type code) read by the test circuit. In some examples, an excitation signal of a predetermined voltage is applied to the sensor circuit to determine a coarse impedance measurement to determine the internal impedance range of the sensor circuit and the signal gain is set accordingly.

FIG. 6 is circuit diagram of portions of another example of a test circuit 604 electrically coupled to a sensor circuit 606. The test circuit can be included in an integrated circuit. In certain examples, the sensor circuit is included in the same integrated circuit and the test circuit. The electronic sensor can be an electrochemical sensor or a gas sensor. The impedance of the electronic sensor may change as the sensor is used and measuring the impedance of sensor can be useful to estimate the remaining useful life of the sensor. Determining when the sensor is near the end of its useful li fe may be more important i f the sensor is used to sense a toxic substance or gas.

The test circuit 604 includes an excitation circuit 614 and a measurement circuit 616. The excitation circuit provides an excitation signal for measuring i mpedance. The measurement circuit can include logic circuitry to perform the functions described and may incl ude control circuitry to initiate the

measurements and calculations. To determine an unknown impedance of a sensor circuit Rx, an excitation signal V exc can be applied to the sensor circuit and the sensor current Ix can be measured, where Ix == Vexc/Rx. The same excitation signal Vexc is applied to a known calibration resistance 626 (Real) and the calibration current leal is measured, where leal = V exc Real. Because Vexc is the same in both measurements, the unknown impedance of the sensor can be determined as Rx ^::: RcaK lcal Ix ).

This measurement approach works well if the value of Rx is the same order of magnitude as Real. However, the approach works less well i f the sensor i mpedance is too di fferent from Real. For instance, i f Real is about 200Ω and Vexc is IV, then I exc is about five mil liamps (5mA). If Rx is one megaohm ( 1 ΜΩ). then the Ix is about one microamp ( Ι μΑ). These values of current are too different for the measurement circuitry to provide the desired accuracy. Adding gain to the signal for measurement may also add gain to the signal error, which will increase error in the measurement of the signal.

The test circuit 604 of FIG. 6 includes an adjustable bridge resistance 628 in addition to the calibration resistance. The value of the bridge resistance is adjusted to be between the resistance value of Real and the value of the sensor impedance. The bridge resistance can be an inexpensive resistance circuit and the resistance may not be known to the desired accuracy. The test circuit 604 can include a multiplexer circuit that can be used to selectively apply the excitation signal to the calibration resistance, the adjustable bridge resistance, or the sensor circuit 606.

A first predetermined excitation signal can be applied to Real and the bridge resistance Rb, and a second predetermined excitation signal can be applied to the bridge resistance Rb and the sensor circuit Rx. Different signal gain can be applied to the separate excitation signals and the measured currents can be used to determine the impedance of the electronic sensor.

For instance, the measurement circuit 616 may apply a first excitation signal Vexci to the calibration resistance Real and measure a calibration current leal. The first excitation signal is applied to the bridge resistance Rb and a first bridge current lbi can be measured. The measurement circuit 616 applies a second excitation signal Vexc ₂ to the bridge resistance value and a second bridge current lb.) can be measured. The second excitation signal is applied to the sensor and a sensor current Ix is measured. The impedance of the sensor is determined as

Rx = (Real) (Ical/Ibi) (Ib?./Ix), where Ibi is the current in the bridge resistance when the excitation is Vexci and Ib ₂ is the current in the bridge resistance when the excitation is Vexc ₂ . Because the measurement excitation voltage and gain are the same for each pair of currents measurements, the accuracy of the measurement voltage and the gain in the measurement system is unimportant.

In an example intended to be illustrative and non-limiting, if the sensor impedance is known to be in the range of about 200Ω, and Real is l ki.. the bridge resistance can be 1. 12Xkil In this case the ratio of the bridge resistance and the calibration resistance, and the ratio of the bridge resistance and the sensor impedance may not be too large, and one value of bridge resistance can be used. The measurement circuit may apply an excitation signal to the sensor to get an estimate of the impedance before settin the value of the bridge resistance. The measurement is an estimate because the excitation signal typically doesn ^' t have the required accuracy. The measurement circuit 616 may set the bridge resistance value to a coarse or approximate resistance value prior to more accurately determining the bridge resistance value. The measurement circuit 616 can also be used to measure the resistance of Real if desired. The multiplexer circuit 630 can be used to apply the excitation signal to the calibration resistance and the measurement circuit 616 can calculate the calibration resistance using the excitation signal.

In another example, if the impedance difference between the sensor impedance Rx and the calibration resistance Real is too large, multiple bridge resistance steps can be used to bridge the measurements between Real and Rx. For instance, the measurement circuit 616 may apply a first excitation signal Vex c i to the calibration and the first bridge resistance Rbi to measure the calibration current leal and the first bridge current Ibn as in the previous example, where Ibn is the bridge current for the first bridge resistance value and the first excitation signal. The first bridge resistance value may be set closer to Real than Rx. The measurement circuit 616 applies a second excitation signal to the first bridge resistance value and a second bridge current lb 1 is measured, where I bi is the bridge current for the first bridge resistance value Rbi and the second excitation signal Vexc?..

The bridge resistance is then changed to a second value Rb: that may be closer to Rx than Real. In an example intended to be illustrative and non- limiting, if the sensor impedance is known to be in the range of about 200Ω, and Real is 10kQ, the value of Rbi may be set to 712Ω and Rb? may be 2.53kQ. The second excitation signal Vexc: is applied to the second bridge resistance and a third bridge current lb:: is measured. A third excitation signal Vexc3 is applied to the second bridge resistance Rb?. and a fourth bridge current lb:; is measured, where Ibn is the bridge current for the second bridge resistance value Rb: and the third excitation signal Vexc3, The third excitation signal is then applied to the sensor impedance Rx and the sensor current Ix is measured. The impedance of the sensor Rx can then be determined using the calibration resistance Real, the calibration current IcaJ . the first bridge current Ibn, the second bridge current lb 12, the third bridge current lb?.?., the fourth bridge current lb?;, and the sensor current Ix, by

Rx = (Rcal)(Ical/Ibii)(Ibi2/Ib22)(Ib23/Ix).

FIG. 7 is a flow diagram of an example of a method 700 of controlling a test circuit to measure an internal impedance of an electronic sensor. At 705, a first predetermined excitation signal is applied to a calibration resistance and a calibration current is measured. A bridge resistance value is then selected. In some examples, an approximate or coarse value of the sensor impedance is determined by the test circuit and the bridge resistance value is set accordingly by the test circuit or a user. The test circuit may include a table stored in memory, and the test circuit may set the bridge resistance by using the approximate sensor impedance as an index into the table. At 710, the same first excitation signal is applied to the bridge resistance and a first bridge current is measured.

At 715, a second predetermined excitation signal is applied to the bridge resistance and a second bridge current is measured. At 720, the same second excitation signal is applied to the sensor and a sensor current is measured. At 725, the internal impedance of the sensor is calculated by the test circuit using the calibration resistance, the calibration current, the first bridge current, the second bridge current, and the sensor current. The calculated impedance may then be to a user or process. For example, the internal impedance may be used to gauge the remaining useful life of the electronic sensor.

More than one bridge resistance may be needed. The bridge resistance may be determined according to a ratio. The test circuit may determine the bridge resistance to keep a ratio of the calibration impedance and the bridge impedance to about four. If the ratio of the selected bridge impedance and the approximate sensor value is not also within a desired ratio, the test circuit may select a second bridge resistance that is within the desired ratio of the sensor and within a desired ratio of the first bridge resistance value. The sensor imped ance is then determined using the calibration resistance, the calibration current, four bridge currents and the sensor current as in the example described previously. This approach can be extended. More than two bridge resistances may be needed if the difference in values of the calibration resistance and the sensor impedance is too great.

FIG. 8 is a circuit diagram of portions of another example of a test circuit

804 electrically coupled to a sensor circuit 806. In addition to addressing power consumption and circuit noise, circuits to monitor the output of electronic sensors may need to tailor the output of the sensor circuits to improve accuracy.

The test circuit 804 can be included on an integrated circuit and includes an input to receive an electrical signal from the sensor circuit 806, a DAC circuit 832, a PGA 834, and measurement circuit 836. In certain examples, the sensor circuit is included on the same integrated circuit and the test circuit. The sensor can be used to detect a concentration of a chemical or gas within the

environment containing the sensor. The internal impedance of the sensor varies with the concentration. The sensor is coupled to a resistive divider that includes a reference resistor 840 ( ref). A switch 842 may enable the resistive divider during measurement of the sensor output. The switch may also be activated for a short time (e.g., 200 microseconds (200us)) to enable the current path through the sensor to briefly heat the sensor and then deactivated to save the power. By measuring Rref, the current can be monitored to precisely control the average power burning on the sensor, to precisely control the temperature to precisely control the sensitivity of the sensor for the measurement.

The measurement circuit 836 may include a controller to open the switch to conserve energy when a measurement is not performed. The voltage Vcc applied to the sensor is divided by the internal impedance of the sensor 806 and the reference resistor 840. To monitor the sensor, the voltage of the signal from the sensor varies with the concentration of the chemical or gas. For instance, the sensor may be a gas sensor. The internal impedance of the sensor may vary with the gas concentration and provide a voltage proportional to a concentration of the gas.

The signal from the sensor circuit 806 includes a direct current (DC) offset and a varying signal component. The DC offset can occur when the internal impedance of the sensor circuit has an approximate impedance that varies by a smal l amount. For example, the internal impedance of the sensor may vary from between 18Ω-20Ω over the range of the concentration of the gas. The voltage due to the 8Ω would appear as a DC offset in the electrical signal from the sensor.

FIG. 9 are graphs o an example of the output of the sensor circuit 806 as a function of the concentration of a gas. The DC component is shown as Vshift. Graph 905 shows that the voltage output varies between 2.37 Volts (2.37V) and 2.5V. The DC offset prevents using a lower voltage measurement circuit if desired and can limit the measurable range of the change in the output, which can impact accuracy of the measurement. To improve accuracy, the DC offset is removed. Graph 910 shows the output of the sensor after shiftin the output to be centered on zero volts and signal gain applied to the signal from the sensor. The graph 910 shows that the accuracy of the measurement can be improved by the larger signal range, and a measurement circuit with a lower voltage can be used to monitor the output.

The test circuit 804 includes a DAC circuit 832 to remove the DC offset in the signal received from the sensor. The DAC circuit 832 can be programmed be user to subtract a known DC offset or automatically adjusted by a control circuit to subtract a measured DC offset. The PGA 834 applies signal gain to the signal shifted by the DAC circuit. The amount of gain provided by the PGA 834 may also be set by a user or automatically adjusted using a control circuit. The measurement circuit 836 generates a measure of the varying signal component. In some embodiments, the measurement circuit 836 includes an analog-to-digital converter (ADC) circuit 838 to generate a digital value representative of the signal form the sensor circuit 806. In the example of FIG. 8, the ADC circuit is a sixteen bit ADC circuit. The signal gain provided by the PGA allows for more signal swing that makes the accuracy of the 16-bit ADC more useful.

Depending on the application, the measurement circuit may also include a fast Fourier transform (FFT) circuit configured to measure a frequency response of the varying signal component.

FIG. 10 is a flow diagram of an example of a method 1000 of controlling a test circuit to measure an internal impedance of an electronic sensor. At 1005, an input signal is received by the test circuit from the electronic sensor. The input signal includes a DC offset component and a varying signal component. At 1010, the DC offset is removed from the input signal using a DAC circuit and signal gain is applied to the remaining the varyin signal component. At 1015, the varyin signal component with the applied signal gain is measured using a measurement circuit. The measure can include a digital value determined using an ADC circuit. The measurement can be provided to one or both of a user or process. For instance, the sensor may be an oxygen sensor. As shown in FIG. 8, the test circuit can include a detection circuit 844. The detection circuit may generate an indication of a lower explosive limit ( LED accordin to the measure of the varyin signal component. The indication may be used to generate an alert regarding the LEL.

The devices, methods, and systems described herein allow for monitoring smart sensors with low power consumption, improved accuracy.

ADDITIONAL DESCRIPTION

The above detailed description includes references to the accompanying drawings, which form a part of the detailed description. The drawings show, by way of illustration, specific embodiments in which the invention can be practiced. These embodiments are also referred to herein as "examples." Ail publications, patents, and patent documents referred to in this document are incorporated by reference herein in their entirety, as though individually incorporated by reference. In the event of inconsistent usages between this document and those documents so incorporated by reference, the usage in the incorporated reference(s) should be considered supplementary to that of this document; for irreconci lable inconsistencies, the usage in this document controls.

In this document, the terms "a" or "an" are used, as is common in patent documents, to include one or more than one. independent of any other instances or usages of "at least one" or "one or more." In this document, the term "or" is used to refer to a nonexclusive or. such that "A or B" includes "A but not B," "B but not A," and "A and B," unless otherwise indicated. In the appended claims, the terms "including ^" and "in which" are used as the plain-English equivalents of the respective terms "comprising ^" and "wherein." Also, in the following clai ms, the terms ^" including ^" and "comprising ^" are open-ended, that is, a system, device, article, or process that includes elements in addition to those listed after such a term in a claim are still deemed to fall within the scope of that claim. Moreover, in the following claims, the terms "first," "second," and "third," etc. are used merely as labels, and are not intended to impose numerical requirements on their obj ects. Method examples described herein can be machine or computer-implemented at least in part.

The above description is intended to be illustrative, and not restrictive.

For example, the above-described examples (or one or more aspects thereof) may be used in combination with each other. Other embodiments can be used, such as by one of ordinary skill in the art upon reviewing the above description. The Abstract is provided to comply with 37 C. F. R. §1.72(b), to allow the reader to quickly ascertain the nature of the technical disclosure. It is submitted with the understanding that it will not be used to interpret or limit the scope or meaning of the claims. Also, in the above Detailed Description, various features may be grouped together to streamline the disclosure. This should not be interpreted as intending that an unclaimed disclosed feature is essential to any clai m. Rather, inventive subject matter may lie in less than all features of a particular disclosed embodiment. Thus, the following claims are hereby incorporated into the Detailed Description, with each claim standing on its own as a separate embodiment. The scope of the invention should be determined with reference to the appended claims, alon with the full scope of equivalents to which such claims are entitled.