DESCRIPTION

ILLUMINATING LAMP CONTROL METHOD AND ILLUMINATING

LAMP CONTROL APPARATUS

Technical Field [0001]

The present invention relates to an illuminating lamp control method and an illuminating lamp control apparatus .

Background Art [0002]

A general fluorescent light as an illuminating lamp includes, a fluorescent glass tube; a heater where an emitter for lighting is coated; gas containing mercury atoms encapsulated inside the fluorescent glass tube; and a fluorescent body coated on the interior of the fluorescent glass tube. At an occasion of lighting a fluorescent light, a current is caused to flow through a heater to heat the heater. When the heater is heated, the emitter coated on the heater emits electrons (thermal electrons) with increased kinetic energy to start discharging. The emitted thermal electrons clash with the mercury- atoms of the gas to emit ultraviolet. When the ultraviolet crashes with the fluorescent body, the fluorescent body emits visible light toward outside through the fluorescent glass tube. Based on such a

principle, a fluorescent light provides visible light. [0003]

In order to realize energy saving technologies of such fluorescent light, conventionally, light controlling by applying power supply inverter technologies and light-out operations in the case where no fluorescent light is used is carried out. Those inverter technologies realize energy saving by controlling light to reduce applied voltage to the fluorescent light in the case where use of fluorescent light is given up. In addition, with the light-out operation when a fluorescent light is no longer used, the applied voltage to the fluorescent light is cut off. Thereby energy saving is realized. [0004]

However, power supply inverter technologies as in conventional energy saving technologies give rise to such a problem that an existing fluorescent light has to be replaced by a fluorescent light of an inverter system and is very costly. In addition, a light-out habit when using a fluorescent light is given up results in an increase in the number of light-out operation and lighting of the illuminating lamp. However, the current flowing through a heater at the time of lighting of a fluorescent light consumes the emitter coated on the heater. Therefore the increase in the number of light-out of the illuminating lamp gives rise to such a problem of reduction of the life of a fluorescent light. In addition, it is generally

said that the life of a fluorescent light gets shorter by an hour at that one lighting operation. Accordingly, the conventional fluorescent light gives rise to such a problem that the energy saving technologies and life extension technologies cannot be realized simultaneously. In addition, that problem is not limited to fluorescent lights but is likewise given rise to the other illuminating lamps.

[0005]

Therefore, the present invention has been made in view of the above described problems, and an object of the present invention is to provide a novel and improved illuminating lamp control method and a novel and improved illuminating lamp control apparatus capable of simultaneously realizing energy saving technologies and life extension technologies of an illuminating lamp for low costs.

[0006]

[Patent Document 1] Japanese Patent Application Laid-Open No. 2004-260991

Summary of the Invention [0007]

In order to solve the above described problems, according to some ways of the present invention, there is provided an illuminating lamp control method of controlling a voltage applied to the illuminating lamp corresponding with a use state of the illuminating lamp with an illuminating lamp control

apparatus comprising a magnetic energy recovery bidirectional current switch brought into series connection between an illuminating lamp and an alternating power supply and a control apparatus controlling the magnetic energy recovery bidirectional current switch; and continuously applying, to an illuminating lamp, a low voltage larger than zero and less than a rated voltage of the illuminating lamp in the case where the illuminating lamp is not used. [0008]

According to such a configuration, a control apparatus controls a magnetic energy recovery bidirectional current switch and generates a voltage applied to an illuminating lamp based on a voltage supplied from an alternating power supply corresponding with a use state. That is, in the case where an illuminating lamp is not used, the control apparatus controls the magnetic energy recovery bidirectional current switch so as to output a low voltage larger than zero and less than the rated voltage of the illuminating lamp and the illuminating lamp accepts that application of the low voltage. In addition, in the case where the illuminating lamp is not used, in order not to make the voltage to be applied to the illuminating lamp zero, the relevant illuminating lamp keeps emitting light due to the low voltage. Accordingly, since the illuminating lamp is not put out and therefore is not required to be put

on. No electromotive force does have to be applied to the emitter at an occasion of putting the illuminating lamp on. [0009]

In addition, in the case of selecting light-out with a switch for switching lighting/light-out of an illuminating lamp, a low voltage can be applied to the illuminating lamp. According to such a configuration, lighting/light-out of an illuminating lamp is selectively switched by a switch and a low voltage is applied to the illuminating lamp selectively only at the light-out time. [0010]

In addition, a low voltage can be applied to an illuminating lamp in the case where no object is detected by an object detection sensor detecting presence of an object within an illumination range of an illuminating lamp. According to such a configuration, lighting/light-out of an illuminating lamp is selectively switched by an object detection sensor so that a low voltage is applied to the illuminating lamp selectively only at the light-out time . [0011]

In addition, in the case where no object is detected by the object detection sensor for not less than predetermined time, the voltage applied to an illuminating lamp can be made zero. According to such a configuration, if no object is detected by an

object detection sensor for predetermined time, the voltage applied to the illuminating lamp will reach zero so that the illuminating lamp will enter a non- light-emitting state, that is, a light-out state. [0012]

In addition, a magnetic energy recovery- bidirectional current switch can include: a bridge circuit comprising a first reverse conducting semiconductor switch and a fourth reverse conducting semiconductor switch arranged with series connection in a first route with a conducting direction at the time of switching off directed to mutually opposite directions and a second reverse conducting semiconductor switch and a third reverse conducting semiconductor switch arranged with series connection in a second route with a conducting direction at the time of switching off directed to mutually opposite directions; and a capacitor arranged between the first route between the first reverse conducting semiconductor switch and the fourth reverse conducting semiconductor switch and the second route between the second reverse conducting semiconductor switch and the third reverse conducting semiconductor switch; a control apparatus alternately switching ON/OFF the first reverse conducting semiconductor switch as well as the third reverse conducting semiconductor switch and the second reverse conducting semiconductor switch as well as the fourth reverse conducting semiconductor switch at switch

switching timing every half cycle of an alternating power supply; and adjusting a gate phase angle representing time difference between switch switching timing and a zero cross point of alternating power supply voltage to, thereby, apply a low voltage to an illuminating lamp. [0013]

According to such a configuration, the control apparatus alternately switches ON/OFF the first reverse conducting semiconductor switch as well as the third reverse conducting semiconductor switch and the second reverse conducting semiconductor switch as well as the fourth reverse conducting semiconductor switch at a switch switching timing subjected to only displacement of a gate phase angel apart from the zero cross point of alternating power supply voltage. With such switching, a magnetic energy recovery bidirectional current switch charges /discharges the capacitor. In addition, the period of that charge/discharge is determined by a gate phase angle. In the case where that discharge is not carried out sufficiently, the capacitor serves as resistance for a circuit. Accordingly, the magnetic energy recovery bidirectional current switch outputs the low voltage lower than the supplied rated voltage to the illuminating lamp. [0014]

In addition, in order to solve the above described problems, according to some ways of the

present invention, there is provided an illuminating lamp control apparatus comprising: a magnetic energy recovery bidirectional current switch brought into series connection between an illuminating lamp and an alternating power supply and a control apparatus controlling the magnetic energy recovery bidirectional current switch so as to continuously applying, to an illuminating lamp, a low voltage larger than zero and less than a rated voltage of an alternating power supply in the case where the illuminating lamp is not used.

[0015]

According to such a configuration, in the case where the illuminating lamp is not used, the magnetic energy recovery bidirectional current switch controlled by the control apparatus applies a low voltage continuously to an illuminating lamp. A low voltage is applied to the illuminating lamp and the illuminating lamp does not enter a non-light-emitting state but emits light corresponding with the low voltage without being put out. Accordingly, since the illuminating lamp is not put out and therefore is not required to be put on. No electromotive force does have to be applied to the emitter at an occasion of putting the illuminating lamp on.

[0016]

In addition, a magnetic energy recovery bidirectional current switch can include: a bridge circuit comprising a first reverse conducting

semiconductor switch and a fourth reverse conducting semiconductor switch arranged with series connection in a first route with a conducting direction at the time of switching off directed to mutually opposite directions and a second reverse conducting semiconductor switch and a third reverse conducting semiconductor switch arranged with series connection in a second route with a conducting direction at the time of switching off directed to mutually opposite directions; and a capacitor arranged between the first route between the first reverse conducting semiconductor switch and the fourth reverse conducting semiconductor switch and the second route between the second reverse conducting semiconductor switch and the third reverse conducting semiconductor switch; a control apparatus alternately switching ON/OFF the first reverse conducting semiconductor switch as well as the third reverse conducting semiconductor switch and the second reverse conducting semiconductor switch as well as the fourth reverse conducting semiconductor switch at switch switching timing every half cycle of an alternating power supply; and adjusting a gate phase angle representing time difference between switch switching timing and a zero cross point of the alternating power supply voltage to, thereby, apply a low voltage to an illuminating lamp. [0017]

According to such a configuration, the control

apparatus alternately switches ON/OFF the first reverse conducting semiconductor switch as well as the third reverse conducting semiconductor switch and the second reverse conducting semiconductor switch as well as the fourth reverse conducting semiconductor switch at a switch switching timing subjected to only displacement of a gate phase angel apart from the zero cross point of alternating power supply voltage. With such switching, a magnetic energy recovery bidirectional current switch charges /discharges the capacitor. In addition, the period of that charge/discharge is determined by a gate phase angle. In the case where that discharge is not carried out sufficiently, the capacitor serves as resistance for a circuit. Accordingly, the magnetic energy recovery bidirectional current switch outputs the low voltage lower than the supplied rated voltage to the illuminating lamp. [0018]

In addition, in the case of applying a low voltage, the gate phase angle can fall within a range more than 90° and less than 270°. According to such a configuration, the gate phase angle is set to fall within such a range and then the above described discharge is not carried out sufficiently and the capacitor serves as resistance for a circuit. Accordingly, a voltage applied to an illuminating lamp will drop and become a low voltage. [0019]

In addition, the control apparatus can apply, to an illuminating lamp, a low voltage or a lighting voltage not less than a rated voltage selectively based on an output signal of a switch for switching the lighting/ light-out of the illuminating lamp.

According to such a configuration, lighting/light-out of an illuminating lamp is selectively switched by a switch and a lighting voltage or a low voltage is applied to the illuminating lamp selectively. In addition, by applying a lighting voltage, luminance of an illuminating lamp increases. [0020]

In addition, the control apparatus can apply, to an illuminating lamp, a low voltage or a lighting voltage not less than a rated voltage selectively based on an output signal of an object detection apparatus detecting presence of an object within an illumination range of an illuminating lamp. According to such a configuration, lighting/light-out of an illuminating lamp is selectively switched by an object detection sensor so that a lighting voltage or a low voltage is applied to the illuminating lamp selectively. In addition, by applying a lighting voltage, luminance of an illuminating lamp increases. [0021]

In addition, in the case where no object is detected by the object detection sensor for not less than predetermined time, the control apparatus can

apply a voltage to the illuminating lamp. According to such a configuration, if no object is detected by an object detection sensor for predetermined time, voltage applied to the illuminating lamp will reach zero so that the illuminating lamp will enter a non- light-emitting state, that is, a light-out state.

Brief Description of the Drawings [0022]

Fig. 1 is a schematic diagram illustrating a configuration of an illuminating lamp control apparatus related to a first embodiment of the present invention;

Fig. 2 illustrates timing charts illustrating relations between power supply voltage of an alternating power supply and control signals controlling a magnetic energy recovery bidirectional current switch related to the present embodiment;

Fig. 3A illustrates conceptual diagrams illustrating operations and currents of a magnetic energy recovery bidirectional current switch related to the present embodiment at α=0°;

Fig. 3B illustrates conceptual diagrams illustrating operations and currents of a magnetic energy recovery bidirectional current switch related to the present embodiment at α=180°;

Fig. 4 illustrates conceptual diagrams illustrating operations and currents of a magnetic energy recovery bidirectional current switch related

to the present embodiment at 0°<α<90°;

Fig. 5 illustrates conceptual diagrams illustrating operations and currents of a magnetic energy recovery bidirectional current switch related to the present embodiment at 90°<α<180°;

Fig. 6 is a diagram illustrating relation between load voltages applied to an illuminating lamp and gate phase angles related to an experiment example;

Fig. 7 illustrates a drive waveform plane illustrating driving operations of an illuminating lamp control apparatus related to the first embodiment of the present invention;

Fig. 8 is a schematic diagram illustrating a configuration of an illuminating lamp control apparatus related to a second embodiment of the present invention; and

Fig. 9 illustrates a drive waveform plane illustrating driving operations of an illuminating lamp control apparatus related to the present embodiment .

Detailed Description of the Preferred Embodiments [0023]

The preferable embodiments of the present invention will be described in detail with reference to the accompanying drawings. Here, in the present specification and the drawings, like reference characters designate the substantially functions and components throughout the' figures thereof to omit

repetitious description. [0024]

(First Embodiment)

At first, a configuration of an illuminating lamp control apparatus 100 related to a first embodiment of the present invention will be described with reference to Fig. 1. Fig. 1 is a schematic diagram illustrating a configuration of an illuminating lamp control apparatus 100 related to the present embodiment . [0025]

As illustrated in Fig. 1, the illuminating lamp control apparatus 100 is connected to an illuminating lamp 10, an alternating power supply 20 and a user switch 30. In addition, the illuminating lamp 10, the alternating power supply 20 and the illuminating lamp control apparatus 100 are brought into a series connection. The alternating power supply 20 supplies the illuminating lamp control apparatus 100 with power supply voltage V having a rated voltage Va for the illuminating lamp 10. The user switch 30 is a switch switching lighting/light-out (ON/OFF) of the illuminating lamp 10 by a user and supplies the illuminating lamp control apparatus 100 with an output signal when lighting is selected. The illuminating lamp control apparatus 100 transforms the power supply voltage V corresponding with lighting/light-out switching operations on the user switch 30 to apply a load voltage Vload to the

illuminating lamp 10. The illuminating lamp 10 accepting the applied load voltage Vload emits light. Here, the illuminating lamp 10 can be a general illuminating lamp such as a fluorescent light, a sodium lamp, a metal halide lamp and a mercury lamp, for example. The illuminating lamp 10 will be described hereinafter as a fluorescent light. [0026]

In addition, here, the alternating power supply 20 is assumed to apply, to the illuminating lamp control apparatus 100, power supply voltage V having a rated voltage Va for the illuminating lamp 10. Hereinafter, the alternating power supply 20 will be described to be dedicated to the illuminating lamp 10 and supplies power supply voltage V having a rated voltage Va for the illuminating lamp 10. However, the alternating power supply 20 will not be limited hereto. For example, the alternating power supply 20 can have another rated voltage and increase and decrease the relevant rated voltage to the rated voltage Va for the illuminating lamp 10 and, thereafter supply the illuminating lamp control apparatus 100 with voltage as a power supply voltage V having a rated voltage Va. [0027]

The illuminating lamp control apparatus 100 includes a magnetic energy recovery bidirectional current switch 110, a gate phase control apparatus 120 (control apparatus) and a phase detector 130.

The magnetic energy recovery bidirectional current switch 110 is brought into a series connection between the alternating power supply 20 and the illuminating lamp 10. The phase detector 130 is connected to the gate phase control apparatus 120 and is connected to a lead between the alternating power supply 20 and the magnetic energy recovery bidirectional current switch 110 and a lead between the magnetic energy recovery bidirectional current switch 110 and the illuminating lamp 10. The gate phase control apparatus 120 is connected to the user switch 30 and the magnetic energy recovery- bidirectional current switch 110. [0028]

In addition, the magnetic energy recovery bidirectional current switch 110 transforms the power supply voltage V having a rated voltage Va supplied from the alternating power supply 20 to apply the load voltage Vload to the illuminating lamp 10. The phase detector 130 taps the voltage between the alternating power supply 20 and the magnetic energy recovery bidirectional current switch 110 and between the magnetic energy recovery bidirectional current switch 110 and the illuminating lamp 10; detects the phase of the load voltage Vload; taps the power supply voltage V between the alternating power supply 20 and the magnetic energy recovery bidirectional current switch 110; detects the phase of the power supply voltage; and supplies the gate phase control

apparatus 120 with phase information. The gate phase control apparatus 120 exemplifies the control apparatus; receives an output signal from the user switch 30; and supplies the magnetic energy recovery- bidirectional current switch 110 with a control signal based on the phase information from the phase detector 130. With the relevant control signal, the magnetic energy recovery bidirectional current switch 110 transforms the power supply voltage V having a rated voltage Va supplied from the alternating power supply 20 to apply the load voltage Vload to the illuminating lamp 10. Here, that phase detector 130 can use a general phase detector and the like. Therefore detailed description will be omitted. In addition, transforming the above described power supply voltage V and the like will be described in detail later. [0029]

In addition, the user switch 30 is connected to the gate phase control apparatus 120. In the case of using the relevant illuminating lamp 10, that is, in the case where the user switch 30 is put ON, the user switch 30 supplies the gate phase control apparatus 120 with an output signal for lighting the illuminating lamp 10. In addition, in the case where the relevant illuminating lamp 10 is not used, that is, the user switch 30 is put OFF, the user switch 30 blocks the above described output signal. Here, in the case where the user switch 30 is put OFF, the

user switch 30 can block the above described output signal and, thereafter, supply the gate phase control apparatus 120 with the output signal for lighting out the illuminating lamp 10. In addition, in the case where the user switch 30 is put OFF, the user switch 30 will be described below in the assumption of blocking the output signal for lighting the illuminating lamp 10. [0030]

The schematic configuration of the magnetic energy recovery bidirectional current switch 110 and the configuration of the exterior thereof have been described so far. Next, with reference to Fig. 1, a configuration of the magnetic energy recovery bidirectional current switch 110 will be described in detail . [0031]

(Configuration of Magnetic Energy Recovery Bidirectional Current Switch 110)

As illustrated in Fig. 1, the magnetic energy- recovery bidirectional current switch 110 is configured by a bridge circuit configured by a first to a fourth reverse conducting semiconductor switches 111 to 114 and a capacitor C connected between a direct current terminal b (hereinafter to be referred to as terminal b) and a direct current terminal c (hereinafter to be referred to as terminal c) of that bridge circuit. In addition, the respective reverse conducting semiconductor switches 111 to 114 are

connected to the gate phase control apparatus 120 and receive control signals. In addition, the bridge circuit is brought into series connection between the alternating power supply 20 and the illuminating lamp 10.

[0032]

The above described configuration is described in further detail as follows. At first, the bridge circuit includes a first route Ll being a route from the alternating current terminal a (hereinafter to be referred to as terminal a) connected to the alternating power supply 20 to the alternating current terminal d (hereinafter to be referred to as terminal d) connected to the illuminating lamp 10 through the terminal b and a second route L2 being a route from the terminal a to the terminal d through the terminal c. In addition, in the first route Ll, the first reverse conducting semiconductor switch 111 is arranged between the terminal d and the terminal b and the fourth reverse conducting semiconductor switch 114 is arranged between the terminal b and the terminal a. And, in the second route L2, the second reverse conducting semiconductor switch 112 is arranged between the terminal d and the terminal c and the third reverse conducting semiconductor switch 113 is arranged between the terminal c and the terminal a. In addition, the capacitor C is provided between the terminal b and the terminal c.

[0033]

That is, the first reverse conducting semiconductor switch 111 and the second reverse conducting semiconductor switch 112 are brought into parallel connection and the third reverse conducting semiconductor switch 113 and the fourth reverse conducting semiconductor switch 114 are brought into parallel connection. In addition, the first reverse conducting semiconductor switch 111 and the fourth reverse conducting semiconductor switch 114 are brought into series connection and the second reverse conducting semiconductor switch 112 and the third reverse conducting semiconductor switch 113 are brought into series connection. [0034]

In addition, for the convenience at an occasion of describing the configurations of the respective reverse conducting semiconductor switches 111 to 114 and control of the magnetic energy recovery bidirectional current switch 110, as described below, the first to the fourth reverse conducting semiconductor switches 111 to 114 will be divided into two pairs (a first pair and a second pair) pairing the two reverse conducting semiconductor switches 111 to 114 positioned diagonally in the block circuit. That is, the first reverse conducting semiconductor switch 111 and the third reverse conducting semiconductor switch 113 will be described as the first pair below and the second reverse conducting semiconductor switch 112 and the fourth

reverse conducting semiconductor switch 114 will be described as the second pair below.

[0035]

Here, the first to the fourth reverse conducting semiconductor switches 111 to 114 include gate terminals (hereinafter to be referred to as gate) receiving an ON signal supplied from the gate phase control apparatus 120 as a control signal and two source/drain terminals (hereinafter to be referred to as source/drain) serving as input terminals and output terminals. In addition, the respective first to fourth reverse conducting semiconductor switches 111 to 114 cause conduction of currents only to one direction at the time of switch-OFF receiving no ON signal input to the gates and cause conduction of currents to both directions at the time of switch-ON receiving an ON signal to the gates. That is, the reverse conducting semiconductor switches 111 to 114 cause conduction of currents from the source and the drain of a side to the other source/drains of the other side at the time of switch-OFF but cause conduction of currents from the source/drain of both sides to the opposite source/drain at the time of switch-ON. Here, the direction of a current flow provided by the respective reverse conducting semiconductor switches 111 to 114 at the time of switch-OFF will be referred to as a switch forward direction and the direction allowing no current flow at the time of switch-OFF will be referred to as a

switch reverse direction. In addition, a direction causing those switch forward direction and reverse direction to connection to the circuit will be hereinafter referred to as a switch polarity. [0036]

In addition, the reverse conducting semiconductor switches 111 to 114 are arranged so as to make the respective switch polarities as follows. The first reverse conducting semiconductor switch 111 and the second reverse conducting semiconductor switch 112 brought into parallel connection or the third reverse conducting semiconductor switch 113 and the fourth reverse conducting semiconductor switch 114 have reversely directed switch polarities. In addition, the first reverse conducting semiconductor switch 111 and the fourth reverse conducting semiconductor switch 114 brought into series connection or the second reverse conducting semiconductor switch 112 and the third reverse conducting semiconductor switch 113 have reversely directed switch polarities as well, Accordingly, the first pair of the first reverse conducting semiconductor switch 111 and the third reverse conducting semiconductor switch 113 have switch polarities in the same direction and the second pair of the second reverse conducting semiconductor switch 112 and the fourth reverse conducting semiconductor switch 114 have switch polarities in the same direction as well. In addition, the switch polarity of the first pair and

the switch polarity of the second pair will be reversely directed.

[0037]

That is, in the case of applying a voltage between the terminal a and the terminal d, the first pair of the reverse conducting semiconductor switches

111 and 113 is brought into conduction only in the direction causing a current to flow from the terminal d to the terminal a at the OFF time and the second pair of the reverse conducting semiconductor switches

112 and 114 is brought into conduction only in the direction causing a current to flow from the terminal a to the terminal d at the OFF time. That is, the forward direction of the switches of the first pair of the reverse conducting semiconductor switches 111 and 113 is the direction from the terminal d to the terminal a and the forward direction of the switches of the second pair of the reverse conducting semiconductor switches 112 and 114 is the direction from the terminal a to the terminal d. However, such switch polarities can be configured oppositely between the first pair of the reverse conducting semiconductor switches 111 and 113 and between the second pair of the reverse conducting semiconductor switches 112 and 114. However, the configuration and operations at that occasion is likewise the above described configuration and operation to be described below and, therefore, description thereof will be omitted here.

[ 0 0 3 8 ]

The configuration of the first to the fourth reverse conducting semiconductor switches 111 to 114 illustrating the above described operations can be considered variously but, for the convenience of description, will be described to be configured by parallel connection between a semiconductor switch and a diode. That is, the respective first to fourth reverse conducting semiconductor switches 111 to 114 include single diodes Dl to D4 and single semiconductor switches Sl to S4 brought into parallel connection to the relevant diodes. In addition, Fig. 1 illustrates the respective first to the fourth reverse conducting semiconductor switches 111 to 114 forms, as described above, parallel connection between the single diodes Dl to D4 and the single semiconductor switches Sl to S4. [0039]

In addition the respective gates of the semiconductor switches Sl to S4 will be referred to as gates Gl to G4. The gates Gl to G4 are respectively brought into connection to the gate phase control apparatus 120 and receive inputs of ON signals supplied as control signals from the gate phase control apparatus 120 to the magnetic energy recovery bidirectional current switch 110 to put ON the semiconductor switch. In the case where the ON signal is input, the semiconductor switches Sl to S4 will enter an ON state to cause conduction of

currents in both directions. However, in the case where no ON signal is input, the semiconductor switches Sl to S4 will enter an OFF state to allow no conduction of currents to any direction. Accordingly, at the time of switching OFF the semiconductor switches Sl to S4, currents are brought into conduction only in the conducting directions of the diodes Dl to D4 brought into parallel connection. Accordingly, operations to be provided to the reverse conducting semiconductor switches 111 to 114 as described above can be illustrated. [0040]

However, the reverse conducting semiconductor switch of the present invention will not be limited to the configurations of the first to the fourth reverse conducting semiconductor switches 111 to 114. That is, the reverse conducting semiconductor switch only has to be a configuration presenting the above described operations and can be, for example, a power MOS FET and a reverse conducting GTO thyristor and can be parallel connection between a semiconductor switch such as an IGBT and the like and the diode. [0041]

In addition, the switch polarities of the above described respective reverse conducting semiconductor switches 111 to 114 will be replaced by the diodes Dl to D4 and will be described as follows. That is, the switch forward directions (the directions of conduction at the time of switching off) are the

conducting directions of the respective diodes Dl to D4 and the switch reverse directions (the directions of no conduction at the time of switching off) are the non-conducting directions of the respective diodes Dl to D4. In addition, the mutual conducting directions of the diodes (Dl and D2 or D3 and D4) brought into parallel connection are mutually directed reversely. The mutual conducting directions of the diodes (Dl and D4 or D2 and D3) brought into series connection are mutually directed reversely as well. In addition, the conducting directions of the first pair of the mutual diodes (Dl and D3) are mutually the same and the conducting directions of the second pair of the mutual diodes (D2 and D4) are mutually the same as well. Accordingly, the conducting directions of the first pair of the diodes (Dl and D3) and the second pair of the diodes ( D2 and D4 ) are mutually directed reversely. [0042]

So far, with reference to Fig. 1, the configuration of the illuminating lamp control apparatus 100 related to the present embodiment has been described in detail. Here, the magnetic energy recovery bidirectional current switch 110 having the above described configuration is a bidirectional current switch recovery magnetic energy disclosed in the Japanese Patent Application Laid-Open No. 2004- 260991 and acts as a static capacitor. That is, the magnetic energy recovery bidirectional current switch

110 is configured by a bridge circuit configured by four reverse conducting semiconductor switches and a capacitor brought into connection between the direct current terminals of the relevant bridge circuit to accumulate magnetic energy at the time of the above described current blocking. In the present embodiment, the magnetic energy recovery bidirectional current switch 110 is controlled to be described below to control the load voltage Vload. Next, with reference to Fig. 2 to Fig. 6, operations of the magnetic energy recovery bidirectional current switch 110 with a control signal from the gate phase control apparatus 120 will be described and the load voltage Vload applied to the illuminating lamp 10 by those operations will be described in detail. [0043]

(Operation of Magnetic Energy Recovery Bidirectional Current Switch 110)

At first, with reference to Fig. 2, a control signal supplied from the gate phase control apparatus 120 to the magnetic energy recovery bidirectional current switch 110, that is, the ON signal applied from the gate phase control apparatus 120 to the gates Gl to G4 of the respective semiconductor switches Sl to S4 will be described. Fig. 2 illustrates timing charts illustrating relations between the power supply voltage V of the alternating power supply 20 and control signals controlling a magnetic energy recovery bidirectional current switch

1 1 0 . [ 0 0 4 4 ]

A waveform 201 in Fig. 2 represents chronological changes of the power supply voltage V supplied by the alternating power supply 20, where the horizontal axis represents the lapse of time and the vertical axis represents the amplitude of voltage. The power supply voltage V is expressed by a sine wave having a rated voltage Va as an amplitude and having a period T. In addition, the voltage applied in the direction of the arrow V indicated downward the alternating power supply 20 in Fig. 1 is taken as the positive voltage and the voltage applied in the opposite direction is taken as the negative voltage. [0045]

The waveform 202 in Fig. 2 schematically illustrates control signal to the gates Gl to G4 and illustrates a drive waveform of the respective semiconductor switches Sl to S4. The horizontal axis represents the lapse of time which is the same as the lapse of time of the above described power supply voltage V and the vertical axis represents the state where the respective semiconductor switches Sl to S4 are switched ON with the control signal to the respective gates Gl to G4. That is, at arbitrary time points (for example, tl) on the time axis in the waveform 201 in Fig. 2 represents the same time point as the corresponding time point (tl) on the time axis in the waveform 202 in Fig. 2. In addition, in the

horizontal axis of the waveform 202 in Fig. 2, a value "Sl, S3 ON" represents the states of the respective semiconductor switches Sl to S4 with an ON signal (control signal) being applied from the gate phase control apparatus 120 to the first pair of the gates Gl and G3 so that the first pair of the semiconductor switches Sl and S3 are simultaneously switched ON and the second pair of the semiconductor switches S2 and S4 are switched OFF. In addition, the value "S2, S4 On" likewise represents the states of the respective semiconductor switches Sl to S4 with an ON signal (control signal) being applied from the gate phase control apparatus 120 to the second pair of the gates G2 and G4 so that the second pair of the semiconductor switches S2 and S4 are simultaneously switched ON and the first pair of the semiconductor switches Sl and S3 are switched OFF. The timing when ON signals are applied from the gate phase control apparatus 120 to the respective gates Gl to G4 will be described below at timing when the respective semiconductor switches Sl to S4 are switched ON/OFF. [0046]

In the waveform 202 in Fig. 2, the first pair of the semiconductor switches Sl and S3 are switched ON for the period from the time point 0 to the time point 1/2T and the second pair of the semiconductor switches S2 and S4 are switched ON for the period from the time point 1/2T to the time point T.

[ 0 0 4 7 ]

In addition, as time point 1/2T and the time point T, the time point of switching from the state where one pair of the semiconductor switches are switched ON and to the state where the other pair of the semiconductor switches are switched ON is called switch switching timing. As illustrated in Fig. 1, the switch switching timing is repeated in the period 1/2T being a half period of the period T of the power supply voltage. Accordingly, the first pair of the first reverse conducting semiconductor switch 111 and the third reverse conducting semiconductor switch 113 and the second pair of the second reverse conducting semiconductor switch 112 and the fourth reverse conducting semiconductor switch 114 are alternately switched ON/OFF in the period 1/2T. [0048]

The waveform 203 in Fig. 2 is a drive waveform of the respective semiconductor switches Sl to S4 subjected to an advance of the switch switching timing in the waveform 202 in Fig. 2 only by the time interval α. In addition, the time interval α is standardized by the waveform 201 in Fig. 2. In addition, in the waveform 202 in Fig. 2, the respective switch switching timing is located at the same time points as the zero cross points (time point 1/2T and time point T) representing the time points when the power supply voltage of the alternating power supply 20 reaches zero. That is, in the

waveform 202 in Fig. 2, the switching ON/OFF of the semiconductor switches Sl to S4 takes place at the zero cross points. However, in the waveform 203 in Fig. 2, the time difference of only the time interval α is present between the respective switch switching timing and the zero cross points since the respecting switch switching timing has been advanced only by time interval α. That time interval α will be hereinafter referred to as a gate phase angle α. [0049]

That is, the gate phase angle α of the waveform

202 in Fig. 2 becomes zero (α=0°) since the respective switch switching timing and the zero cross point come at the same time point. In addition, in the waveform

203 in Fig. 2, the gate phase angle α is illustrated to be a value larger than 0° and less than 90° (0°<α<90°, for example, 45°) . Here the gate phase angle α being the time difference being an angle corresponds with an occasion of expressing the period

T of the power supply voltage V as a phase 360°. [0050]

In addition, the wave forms 204 to 206 in Fig. 2 are drive waveforms subjected to an advance of the switch switching timing of the wave form 202 in Fig. 2 only by the gate phase angle α likewise the waveform represented by the waveform 203 in Fig. 2. In addition, in the waveform 204 in Fig. 2, the gate phase angle α is 90° (α=90°) . In the waveform 205 in Fig. 2, the gate phase angle α is larger than 90° and

less than 180° ( 90°<α<l 80° ) . In the waveform 206 in Fig. 2, the gate phase angle α is 180° (α=180°) . [0051]

Next, with reference to Figs. 2 to 5, in the case of changing the gate phase angle α, the change of the current I flowing inside the magnetic energy recovery bidirectional current switch 110 and the load voltage Vload (voltage applied to the illuminating lamp 10) being output from the magnetic energy recovery bidirectional current switch 110 will be described in detail. That is, by changing timing switching ON/OFF of the respective semiconductor switches Sl to S4 for the change of the power supply voltage V, the load voltage Vload being output changes. Here, the gate phase angle α will be simply referred to as angle α. In addition, the case where the angle α is set to 0° to 180° will be described below. The reason thereof is that the change of the current I and the load voltage Vload in the case of setting the angle α to 180° to 360° is likewise the case of setting the angle α to 0° to 180°. [0052]

Fig. 3A illustrates conceptual diagrams illustrating operations and currents I of a magnetic energy recovery bidirectional current switch 110 at α=0°. Fig. 3B illustrates conceptual diagrams illustrating operations and currents I of a magnetic energy recovery bidirectional current switch 110 at α=180°. Fig. 4 illustrates conceptual diagrams

illustrating operations and currents I of a magnetic energy recovery bidirectional current switch 110 at 0°<α<90°. Fig. 5 illustrates conceptual diagrams illustrating operations and currents I of a magnetic energy recovery bidirectional current switch 110 at 90°<α<180°. In addition, in order to make the following description easy to understand, Fig. 3A to Fig. 5 illustrate only the block circuit of the magnetic energy recovery bidirectional current switch 110 and the alternating power supply 20. Accordingly, the configurations of the block circuits in Fig. 3A to Fig. 5 are likewise the configuration of the block circuit of the magnetic energy recovery bidirectional current switch 110 in Fig. 1. The configurations omitted in Fig. 3A to Fig. 5 are likewise the configuration in Fig. 1. In addition, in Fig. 3A to Fig. 5, the reference characters are omitted appropriately but will be taken as being designated by the like reference characters as the reference characters in Fig. 1. In addition, in Fig. 3A to Fig. 5, the semiconductor switches Sl to S4 will not be illustrated at the time of switch-OFF but only illustrated in the full line as the route bypassing and going around the diodes Dl to D4 brought into parallel connection only at the time of switch-ON. The respective semiconductor switches Sl to S4 herein conceptually represent to bring the respective source/gate into conduction at the time of switch-ON and block the respective source/gate at the time of

switch-OFF. In addition, the semiconductor switch Sl and the semiconductor switch S3 will be referred to as a first pair below and the semiconductor switch S2 and the semiconductor switch S4 will be referred to as a second pair below. [0053]

At first, with reference to Fig. 3A, the case of α= 0° will be described. In addition, the current flows at the representative time points tl and t4 in Fig. 2 will be described. At the time point tl

(t=tl), the power supply voltage V is applied in the positive direction so that only the first pair is switched ON and at the time point t4 (t=t4) , the power supply voltage V is applied in the negative direction so that only the second pair is switched ON,

[0054]

Under the condition of α=0° and t=tl, the current I flows from the alternating power supply 20 through the first route Ll or the second route L2. That is, the current I sequentially passes the diode D4 and the semiconductor switch Sl or sequentially passes the semiconductor switch S3 and the diode D2. Accordingly, the capacitor C basically does not charge nor discharge. That is, the current I does not activate the capacitor C in any way but the power supply voltage V is output directly as the applied voltage Vload. Accordingly Vload=V will be derived.

[0055]

Under the condition of α=0° and t=t4, the current

I flows in the reverse direction in the same route as in the case of α=0° and t=tl. Therefore, description on the flow of that current I will be omitted. In addition, that case will derive Vload=V as well.

[0056]

Next, with reference to Fig. 3B, the case of α=180° will be described. In addition, the current flows at the representative time points tl and t4 in Fig. 2 will be described. At the time point tl

(t=tl), the power supply voltage V is applied in the positive direction so that only the second pair is switched ON and at the time point t4 (t=t4), the power supply voltage V is applied in the negative direction so that only the first pair is switched ON.

[0057]

Under the condition of α=180° and t=tl, the current I sequentially flows from the alternating power supply 20 in the diode D4 or the semiconductor switch S4, the capacitor C and the diode D2 or the semiconductor switch S2. In addition, under the condition of α=180° and t=t4, the current I flows to the alternating power supply 20 sequentially through the diode Dl or the semiconductor switch Sl, the capacitor C and the diode D3 or the semiconductor switch S3. At that occasion, a voltage higher than on the side of the second route L2 is always applied to the side of the first route Ll of the capacitor C. Accordingly, the capacitor C will be substantially brought into series connection between the

alternating power supply 20 and the illuminating lamp 10. Accordingly, together with the reactance component L and the resistance component R of the illuminating lamp 10, the capacitor C will organize an LCR circuit. The detailed description on the current flow at that occasion will be omitted. In addition, the load voltage Vload is schematically expressed by Vload=V-Vc. Here, the voltage drop -Vc takes place by charging the capacitor C.

[0058]

Next, with reference to Fig. 4, the case of 0°<α<90° will be described. In addition, the current flows at the representative time points tl, t2, t3 and t4 in Fig. 2 will be described. At the time point tl (t=tl), the power supply voltage V is applied in the positive direction so that only the first pair is switched ON; at the time point t2

(t=t2), the power supply voltage V is applied in the positive direction so that only the second pair is switched ON; the time point t3 (t=t3), the power supply voltage V is applied in the negative direction so that only the second pair is switched ON; and the time point t4 (t=t4), the power supply voltage V is applied in the negative direction so that only the second pair is switched ON.

[0059]

Under the condition of 0°<α<90° and t=tl, the current I flows the route likewise the route where the current I flows under the condition of α=0° and

t=tl. Accordingly, description on the flow of that current I will be omitted. In addition, the power supply voltage V is output as the load voltage Vload. However, at t=tl, the power supply voltage V increases in the positive direction to a full extent and the substantially maximum voltage of the power supply voltage V in the positive direction can be output as Vload. [0060]

Under the condition of 0°<α<90° and t=t2, the current I flows in the route likewise the route where the current I flows under the condition of α=180° and t=tl. Accordingly, description on the flow of that current I will be omitted as well. However, the time point of t=t2 is immediately prior to the zero cross point where the power supply voltage V shifts from a positive value to a negative value. Therefore, a portion of the voltage in that power supply voltage V is used for charging the capacitor C. That is, positive charges are charged on the side of the first route Ll of the capacitor C and negative charges are charged on the side of the second route L2. In addition, the load voltage Vload is schematically expressed by Vload=V-Vc. [0061]

Under the condition of 0°<α<90° and t=t3, the current I flows the route likewise the route where the current I flows under the condition of α=0° and t=t4. The capacitor C sandwiched by the relevant

routes is charged and capable of discharging electric energy accumulated in the capacitor C. That is, the current I can flow to the alternating power supply 20 sequentially through the semiconductor switch S2, the capacitor C and the semiconductor switch S4 besides the above described routes. In addition, the time point of t=t3 is immediately after the zero cross point where the power supply voltage V shifts from a positive value to a negative value and the power supply voltage V starts increasing (increasing in the absolute value of the power supply voltage V) in the negative direction. Accordingly, at t=t3, the positive charge charged in the capacitor C is discharged from the capacitor C to the alternating power supply 20 through the semiconductor switch S4 and the negative charge is discharged from the capacitor C to the semiconductor switch S2. Accordingly, during discharging the accumulated electric energy, the capacitor C operates likewise a power supply brought into series connection to the alternating power supply 20 to increase the power supply voltage V. That is, the capacitor C will increase the load voltage Vload at t=t3. Accordingly, that load voltage Vload is schematically expressed by Vload=V+Vc and can be a voltage higher than the rated voltage Va of the power supply voltage V. [0062]

Under the condition of 0°<α<90° and t=t4, the current I flows in the route likewise the route where

the current I flows under the condition of α=0° and t=t4. In addition, the time point t4 is a time point subjected to the lapse of sufficient time from the time point t3 and the capacitor C discharges all the accumulated electric energy. Accordingly, the current I flows only in the route likewise the route where the current I flows under the condition of α=0° and t=t4. Accordingly, description on the flow of that current I will be omitted. In addition, the power supply voltage V is output as the load voltage Vload. However, at t=t4, the power supply voltage V increases in the negative direction to a full extent and the substantially maximum voltage of the power supply voltage V in the negative direction can be output as Vload. [0063]

Under the condition of 0°<α<90° and t=t4 and thereafter, the current I flows likewise the current I at the above described tl to t4 with the flowing direction being reversed. Accordingly, description on the flow of that current I will be omitted as well [0064]

The summary on the load voltage Vload in the case of 0°<α<90° as described above will be as follows. At first, at t=tl, the power supply voltage V is directly output as the load voltage Vload. Next, at t=t2, a portion (Vc) of a voltage at an occasion where the power supply voltage V is inversed from the positive direction to the negative direction is

applied to charging the capacitor C. The load voltage Vload temporarily drops. However, at t=t3, the capacitor C discharges charges and serves as a power supply. Therefore, the load voltage Vload is increased only by the electric energy (Vc) of the capacitor C higher than the power supply voltage V. At t=t4, the capacitor C has discharged all the electric energy without carrying out any operations for the current I but the power supply voltage V is directly output as the load voltage Vload.

[0065]

Therefore, consequently, in the case of 0°<α<90°, the load voltage Vload (Vload=V+Vc) can be a voltage higher than the rated voltage Va of the power supply voltage V.

[0066]

Next, with reference to Fig. 5, the case of

90°<α<180° will be described. In addition, the current flows at the representative time points tl, t3, t4 and t5 in Fig. 2 will be described. At the time point tl (t=tl), the power supply voltage V is applied in the positive direction so that only the second pair is switched ON; at the time point t3 (t=t3), the power supply voltage V is applied in the negative direction so that only the second pair is switched ON; at the time point t4 (t=t4), the power supply voltage V is applied in the negative direction so that only the first pair is switched ON; and at the time point t5 (t=t5), the power supply voltage V

is applied in the positive direction so that only the first pair is switched ON.

[0067]

Under the condition of 90°<α<180° and t=tl, the current I flows the route likewise the route where the current I flows under the condition of α=180° and t=tl. Accordingly, description on the flow of that current I will be omitted. The voltage drops due to charging the capacitor C so that the load voltage Vload at that occasion will get lower than the power supply voltage V. That is, the load voltage Vload is schematically expressed by Vload=V-Vc. Here, the voltage drop -Vc takes place by charging the capacitor C. [0068]

Under the condition of 90°<α<180° and t=t3, the current I flows the route likewise the route where the current I flows under the condition of 0°<α<90° and t=t3. That is, likewise the capacitor C 0°<α<90° and t=t3, the capacitor C discharges the accumulated electric energy. Accordingly, during discharging the accumulated electric energy, the capacitor C operates likewise a power supply brought into series connection to the alternating power supply 20 to increase the power supply voltage V. Accordingly, that load voltage Vload is schematically expressed by Vload=V+Vc. Here, the +Vc hereof represents an increase in voltage due to discharging the electric energy form the capacitor C.

[ 0 0 6 9 ]

However, the capacitor C, the reactance component L and the resistance component R organize an LCR circuit. Accordingly, the discharge of the accumulated electric energy takes place later than the switch switching timing when the route for discharging is formed. The period from the time point forming that discharge route to the time point actually starting the discharge of the electric energy will be taken as delay time γ here. In addition, the time point of t=t3 is immediately after the zero cross point where the power supply voltage V shifts from a positive value to a negative value and the power supply voltage V starts increasing

(increasing in the absolute value of the power supply voltage V) in the negative direction. Therefore, the power supply voltage V is not sufficiently large. Accordingly, the power supply voltage V is a load voltage and the voltage Vc from the capacitor C is delayed by the output occasion. Accordingly, prior to a lapse of sufficient time from the time point forming the route for discharging from the capacitor C, the value of the load voltage Vload can be smaller than the value of the voltage V. The case of the load voltage Vload getting smaller than the voltage V will be described later.

[0070]

Under the condition of 90°<α<180° and t=t4, the current I flows, in the reverse direction, in the

route likewise the route where the current I flows under the condition of 90°<α<180° and t=tl. Accordingly, description on the flow of that current I will be omitted. In addition, since the load voltage Vload is likewise in the above described case under the condition of 90°<α<180° and t=tl except that the direction is reversed, description thereof will be omitted. [0071]

Under the condition of 0°<α<90° and t=t5, the current I flows in the route likewise the route where the current I flows under the condition of 90°<α<180° and t=t3. In addition, since the load voltage Vload is likewise in the above described case under the condition of 90°<α<180° and t=t2 except that the direction is reversed, description thereof will be omitted . [0072]

Therefore, consequently, in the case of

90°<α<180°, the load voltage Vload can be a voltage lower than the rated voltage Va of the power supply voltage V (Vload<V) . [0073]

So far, the flow of the current I at the time points tl, t3, t4 and t5 and the load voltage Vload under the condition of 0°<α<180° have been described. Here, an occasion where the load voltage Vload schematically expressed by Vload=V+Vc can be lower than the rated voltage Va under the condition of

90°<α<180° and t=t3 will be schematically described. That occasion will be described with reference to the waveforms 203 to 205 at the time points tl, t3 and t4 as examples . [0074]

At t=tl, the capacitor C is brought into series connection between the alternating power supply 20 and the illuminating lamp 10 so that a portion of the power supply voltage V is applied to charging the capacitor C. Accordingly, a drop in the load voltage Vload took place. At t=t3, the route (herein after to be referred to as discharge route) for discharging the capacitor C is formed and the load voltage Vload was schematically expressed by Vload=V+Vc. [0075]

Here, the period of forming that discharge route is taken as the period β (see the waveform 205 in Fig. 2) . That period β will be a period for forming a discharge route from the capacitor C due to the relation between the ON/OFF states of the semiconductor switches Sl to S4 and the direction for applying the power supply voltage V. In addition, for the waveform 205 in Fig. 2, that period β is, for example, from the time point 1/2T until the next switch switching timing. Accordingly, the gate phase angle α will be derived by subtracting the period β from the period 1/2T. That is, α=l/2T-β and specifically α=180°-β are derived. [0076]

In the waveform 205 in Fig. 2, only the time point t3 is included in the period β. In addition, as in the waveform 202 in Fig. 2, in the case where the time point t4 is included in the period β, the power supply voltage V will be the rated voltage Va so that the load voltage Vload fulfills both expressions of Vload=V+Vc=Va+Vc and Vc>0. Accordingly, the load voltage Vload will not be less than the rated voltage Va. Accordingly, in order to make the load voltage Vload lower than the rated voltage Va, the period β must not include the time point giving rise to V=Va, that is, the time point t4.

Accordingly, the period β will become β<l/4T=90°. [0077]

Therefore, in the case of 90°<α<180°, the load voltage Vload can be lower than the rated voltage Va.

Here, the gate phase angle α is set to fall within the range of 0° to 180°. In addition, the case of the gate phase angle α being 180° to 360° is likewise the case of the gate phase angle α being 180° to 0° and, therefore, description thereon will be omitted.

[0078]

In addition, the gate phase angle α and the period β when the load voltage Vload reaches the voltage not more than the rated voltage Va, that is, the gate phase angle α and the period β giving rise to Vload=Va will be taken as a reference angle αO and a stand period βO.

[0079]

As in the description related to the waveform 205 in Fig. 2 described above, the load voltage Vload will be Vload=V-Vc or Vload=V+Vc in 90°<α<180°. In addition, as described above, under the condition of

90°<α<90°, Vload=V+Vc takes place during the period β. Accordingly, in order that the load voltage Vload gets lower than the rated voltage Va, the case of V+Vc<Va takes place during the period β under the condition of 90°<α<180°. Here, the reference period βO giving rise to Vload=V+Vc=Va being the boundary between V+Vc<Va and V+Vc>Va will be described.

[0080]

In order to realize V+Vc=Va, the voltage Vc, that is, the increase in voltage due to discharging from the capacitor C needs to be larger. In addition, the capacitor C starts discharging as described above after the above described delay time γ. Accordingly, the reference time βO giving rise to V*Vc=Va will become larger than the delay time γ (βθ>γ) . Accordingly, β≤γ will result in β<βθ.

[0081]

Accordingly, the discharge period β is shorter than the delay time γ and then the discharge period β will become shorter than the reference period βO. Accordingly, with the discharge period β being smaller (shorter) than the delay period γ, the load voltage Vload will become small than the rated voltage Va .

[0082]

Consequently, when the gate phase angle α fulfills 90°<α<180°, the load voltage Vload will become smaller than the rated voltage Va. [0083]

So far, the current I and the load voltage Vload output from the magnetic energy recovery bidirectional current switch 110 in the case of changing the gate phase angle α have been described. Next, with reference to Fig. 6, an experiment example of the change in the load voltage Vload when a fluorescent light being the illuminating lamp 10 is actually brought into connection and the gate phase angle α is changed will be described. Fig. 6 is a diagram illustrating relation between voltages (load voltages Vload) applied to the illuminating lamp 10 and gate phase angles related to an experiment example. Here, for the experiment hereof, two 40 W fluorescent lights are used as the illuminating lamp 10. [0084]

As illustrated in Fig. 6, for the experiment example hereof, the load voltage Vload has a size of 105% of the power supply voltage V with the gate phase angle α being 0°. Here, the reason why the load voltage Vload does not get to the same size as the power supply voltage V is that a slight amount of resistance component of the reverse conducting semiconductor switches 111 to 114 activates the capacitor C to charge and discharge a slight amount

of charges. In addition, at an occasion where the gate phase angle α changes from 0° to 90°, the load voltage Vload will become larger than the power supply voltage V. This is caused by operations of the magnetic energy recovery bidirectional current switch 110 under the condition of the above described 0°<α<90°. In addition, at an occasion where the gate phase angle α changes from 90° to approximately 140°, the load voltage Vload is larger than the power supply voltage V. However, as the gate phase angle α gets larger than 90°, the load voltage Vload decreases. The voltage drop described in the description on the operations of the magnetic energy recovery bidirectional current switch 110 under the above described condition of 90°<α<180° causes that voltage drop. In addition, since the discharge period β is not sufficiently short and the above described increase in voltage activates the capacitor C, the load voltage Vload gets larger than the power supply voltage V. And when the gate phase angle α becomes not less than approximately 140°, the load voltage Vload will become lower than the power supply voltage V. Accordingly, in that experiment example, the reference angle αO is approximately 140°. In addition, that voltage drop is due to the voltage drop described in the description on the operations of the magnetic energy recovery bidirectional current switch 110 under the above described condition of 90°<α<180° and α=180°. With the gate phase angle α being not

less than approximately 140°, the load voltage Vload can be made smaller than the power supply voltage V since the discharge period β has got sufficiently short (β<γ) . Here, in the case of setting the gate phase angle α to the reference angle αO (approximately 140°), the load voltage Vload of the same value as the power supply voltage V having the rated voltage Va is applied to the illuminating lamp 10. [0085]

For the experiment example in Fig. 6, the reference angle αO becomes approximately 140°. Accordingly, in the case where the gate phase angle α is larger than approximately 140°, the load voltage Vload gets smaller than the power supply voltage V. However, the present invention will not be limited thereto. That is, that reference angle αO depends on the illuminating lamp 10 and the capacitor C as described above. Actually, due to changes in type, the number of units, reactance component L and resistance component R of the illuminating lamp 10 and electric capacity of the capacitor C and the like, the reference angle αO will become an angle within the range of not less than 90° and less than 180°. Accordingly, in the case of setting the gate phase angle α to larger than 90° and not more than 180°, the load voltage Vload can be smaller than the power supply voltage V. [0086]

In addition, the case where the gate phase angle α falls within the range of 0° to 180° is described above. However, in the case of changing the gate phase angle α from 180° to 360°, the load voltage Vload will become a value likewise the case where the gate phase angle α is caused to change from 180° to 0°, That is, in the case where the gate phase angle α is not less than 0° and not more than the reference angle αO, the load voltage Vload will become not less than the power supply voltage V. In the case where the gate phase angle α is larger than the reference angle αO and not less than 180°, the load voltage Vload will become less than the power supply voltage V. In contrast, in the case where the gate phase angle α is larger than 180° and less than (360° - reference angle αO), the load voltage Vload will become less than the power supply voltage V. In the case of not less than

(360° - reference angel αO) and not more than 360°, the load voltage Vload will become not less than the power supply voltage V. The load voltage Vload in the case of the gate phase angle being 180° to 360° is obtained by operations likewise the operation of the above described magnetic energy recovery bidirectional current switch 110 and, therefore, detailed description thereof will be omitted.

[0087]

Accordingly, by setting the gate phase angle α larger than the reference angle αO and less than (360° - reference angle αO ) , the load voltage Vload can be

made smaller than the power supply voltage V. In the case where two 40 W fluorescent lights are used as the illuminating lamp 10, that is, in the case of the experiment example in Fig. 6, the range of that gate phase angle α will fall within the range of larger than approximately 140° and less than 220°. In addition, since the reference angle αO can be an angle falling within the range of not less than 90° and less than 180°, in the case where the gate phase angle α falls within the range larger than 90° and less than 270°, the load voltage Vload can be smaller than the power supply voltage V.

[0088]

In order to describe operations of an actual illuminating lamp control apparatus 100, at the time of lighting the illuminating lamp 10, setting the gate phase angle α at approximately 140° being the reference angle αO, the load voltage Vload is taken below to be a voltage (hereinafter to be referred to as lighting voltage) equivalent to 100% of the power supply voltage V being the rated voltage Va of the alternating power supply 20. In addition, at the time of putting the illuminating lamp 10 out, setting the gate phase angle α at approximately 180°

(hereinafter to be referred to as light-out angle αl), the load voltage Vload is taken to be a voltage

(hereinafter to be referred to as low voltage) equivalent to approximately 50% of the power supply voltage V.

[ 0 0 8 9 ]

However, the present invention will not be limited thereto. That is, the light-out angle αl of the gate phase angle α at the light-out time can be set so that the load voltage Vload become lower than the power supply voltage V within a range of 90°<α<270°. The gate phase angle α at the lighting time can be set so that the load voltage Vload become not less than the power supply voltage V. Accordingly, the lighting voltage can be set to not less than the rated voltage Va of the power supply voltage V. The low voltage can be set to a voltage less than the rated voltage Va. For example, in Fig. 6, setting the light-out angle αl at approximately 140°, the low voltage can be set to a voltage in the amount of 60% of the power supply voltage V. Setting the lighting angle αl at 90°, the lighting voltage can be set to 140% of the power supply voltage V. Here, in the case where the lighting voltage is not less than the rated voltage Va, the luminance of the illuminating lamp 10 increases since the applied voltage increases. [0090]

So far, with reference to Figs. 2 to 6, operations of the magnetic energy recovery bidirectional current switch 110 by the control signals from the gate phase control apparatus 120 have been described in detail. In addition, the load voltage Vload applied to the illuminating lamp 10 by

those operations has been described in detail as well. Next, with reference to Fig. 7, operations of the illuminating lamp control apparatus 100 will be described and the load voltage Vload actually applied to the illuminating lamp 10 will be described.

[0091]

(Changes in Load Voltage Vload at Light- Out/Lighting of User Switch 30)

Here, with reference to Fig. 7, changes in the load voltage Vload at an occasion of switching the user switch 30 to light-out /light ing will be described. Fig. 7 is a drive waveform plane representing the drive of the illuminating lamp control apparatus 100 related to the present embodiment. In Fig. 7, the upper diagram is a timing chart illustrating occurrences of lighting/light-out

(ON/OFF) switching of the user switch 30 by a user. In addition, the lower diagram is a voltage chart illustrating changes in the load voltage Vload by operating the relevant user switch 30. Here, in both charts, the horizontal axis designates time axis. However, an arbitrary time point (for example, kl) on the time axis of one chart is taken as the same time point as the corresponding time point (kl) on the time axis in the other chart.

[0092]

As illustrated in the upper chart in Fig. 7, the user switch 30 undergoes light-out / lighting switching from the time point 0 until the time point k4. From

the time point 0 until the time point kl, the user switch 30 is selected to lighting. In response, the load voltage Vload is set to a lighting voltage. In addition, the user switch 30 is switched and selected to light-out at the time point kl . Corresponding with that light-out state, the load voltage Vload is set to a low voltage. Accordingly, from the time point kl until the time point k2 , a low voltage is continuously applied to the illuminating lamp 10. In addition, at the time point k2 , the user switch 30 is switched at the time point k2 and selected to lighting again. Corresponding with that lighting state, the load voltage Vload is set to a lighting voltage. Accordingly, from the time point k2 until the time point k3, a lighting voltage is continuously applied to the illuminating lamp 10. In addition, at the time point k3, the user switch 30 is switched and the light-out is selected. Corresponding with that light-out state, the load voltage Vload is set to a low voltage. Accordingly, from the time point k3 to the time point k4, a low voltage is continuously applied to the illuminating lamp 10. In addition, at the time point k4, the user switch 30 is switched and the lighting is selected again. Corresponding with that lighting state, the load voltage Vload is set to a lighting voltage. Accordingly, at and after the time point k4, a lighting voltage is continuously applied to the illuminating lamp 10. [0093]

Next, a flow of outputting a lighting voltage from the illuminating lamp control apparatus 100 during the period of lighting being selected by the user switch 30, for example, from the time point 0 until the time point kl, will be described briefly. At first, the user switch 30 having selected the lighting outputs a predetermined output signal to the gate phase control apparatus 120. The gate phase control apparatus 120 in receipt of the relevant output signal sets the gate phase angle α at a reference angle αO (140°, for example) . In addition, the gate phase control apparatus 120 receives phase information from the phase detector 130. The gate phase control apparatus 120 prepares a control signal (ON signal) from the set gate phase angle α and the phase information to supply the gates Gl to G4 of the magnetic energy recovery bidirectional current switch 110 with the control signal. The magnetic energy recovery bidirectional current switch 110 in receipt of supply of the control signal modulates the power supply voltage V supplied from the alternating power supply 20 to output the load voltage Vload in the size of the lighting voltage (for example, 100% of the rated voltage Va) . The output of the relevant load voltage Vload is triggered by the operations of the above described magnetic energy recovery bidirectional current switch 110. In addition, the magnetic energy recovery bidirectional current switch 110 applies a lighting voltage being the load voltage

Vload to the illuminating lamp 10. Accordingly, the illuminating lamp 10 will emit light corresponding with the lighting voltage at the lighting time, that is, in the case of using the illuminating lamp 10. [0094]

And, a flow of outputting a low voltage from the illuminating lamp control apparatus 100 during the period of light-out being selected by the user switch 30, for example, a period from the time point kl until the time point k2, will be described briefly. At first, the user switch 30 having selected the lighting blocks a predetermined output signal. The gate phase control apparatus 120 lacking an input of the relevant output signal sets the gate phase angle α at a light-out angle αl (180°, for example) . In addition, the gate phase control apparatus 120 receives phase information from the phase detector 130. The gate phase control apparatus 120 prepares a control signal (ON signal) from the set gate phase angle α and the phase information to supply the gates Gl to G4 of the magnetic energy recovery bidirectional current switch 110 with the control signal. The magnetic energy recovery bidirectional current switch 110 in receipt of supply of the control signal modulates the power supply voltage V supplied from the alternating power supply 20 to output the load voltage Vload in the size of he lighting voltage (for example, 50% of the rated voltage Va) . The output of the relevant load voltage

Vload is triggered by the operations of the above described magnetic energy recovery bidirectional current switch 110. In addition, the magnetic energy recovery bidirectional current switch 110 applies a load voltage Vload being the load voltage Vload to the illuminating lamp 10. Accordingly, the illuminating lamp 10 will emit light corresponding with the low voltage at the lighting time, that is, in the case of using the illuminating lamp 10. Accordingly, the applied voltage of the illuminating lamp 10 will not become zero even at the light-out time so that the illuminating lamp 10 will not enter a non-light-emitting state. [0095]

So far, the configuration and the operations of the illuminating lamp control apparatus 100 related to the first embodiment of the present invention have been described in detail. According to the first embodiment of the present invention, in the case of using no illuminating lamp 10, a low voltage not more than the rated voltage Va (power supply voltage V) is applied to the illuminating lamp 10. Accordingly, since the illuminating lamp 10 is not put out (a state that the applied voltage is zero) even in the case of using no illuminating lamp 10, the number of light-out can be reduced. Therefore, according to the illuminating lamp control apparatus 100, the life of the illuminating lamp 10 can be extended. In addition, in the case of using no illuminating lamp

10, a low voltage not more than the rated voltage Va is applied to the illuminating lamp 10. Therefore, compared with the case of using the illuminating lamp 10 in all-time lighting state, electric power consumption can be reduced. Therefore, according to the illuminating lamp control apparatus 100, electric power consumption can be reduced to save energy. [0096]

Accordingly, the illuminating lamp control apparatus 100 related to the present embodiment can attain life extension technologies and energy saving technologies concurrently. In addition, since the life extension on the illuminating lamp 10 can be planned, the number of exchanging the illuminating lamp 10 can be reduced to result in a cost saving and a resource saving. In addition, it is not necessary to switch a fluorescent light to an inverter system likewise in the conventional case. The illuminating lamp control apparatus 100 related to the present embodiment is extremely simply configured and each good is inexpensive. Therefore, according to the present embodiment, compared with the case of exchange with a fluorescent light in a complicated and expensive inverter system, a small amount of cost spending for facility investment will be sufficient. In addition, such an illuminating lamp control apparatus 100 can provide larger effects at an occasion of use in the place where lighting is always required. For example, such a place includes

hallways, factories and offices always requiring lighting. In addition, use thereof in a showroom, a hallway and the like enables attainment of display effects inside a shop, security effects, accident preventing effects, the above described life extension technologies, energy saving technologies and cost reduction.

[0097]

In addition, at the lighting time, that is, in the case of using the illuminating lamp 10, the gate phase angle α is set to an angle not more than the above described reference angle αO or an angle between (360° - reference angle αO) and 360°. Thereby, a voltage not less than the rated voltage Va of the power supply voltage V can be applied to the illuminating lamp 10. Accordingly, luminance of the illuminating lamp 10 at the light time can be increased more than in the case of a conventional illuminating lamp 10.

[0098]

(Second Embodiment)

Next, a configuration of an illuminating lamp control apparatus 200 related to a second embodiment of the present invention will be described with reference to Fig. 8. Fig. 8 is a schematic diagram illustrating a configuration of an illuminating lamp control apparatus 200 related to a second embodiment of the present invention.

[0099]

As illustrated in Fig. 8, the illuminating lamp control apparatus 200 is connected to an illuminating lamp 10, an alternating power supply 20 and a human body detection sensor 40. In addition, the illuminating lamp 10, the alternating power supply 20 and the illuminating lamp control apparatus 200 are brought into a series connection. The alternating power supply 20 supplies the illuminating lamp control apparatus 200 with power supply voltage V having a rated voltage Va for the illuminating lamp 10. Detecting presence of an object within the illuminating range of the illuminating lamp 10, the human body detection sensor 40 emits an output signal but emits no output signal unless detecting an object, The illuminating lamp control apparatus 200 transforms the power supply voltage V corresponding with the output signal of the human body detection sensor 40 to apply a load voltage Vload to the illuminating lamp 10. The illuminating lamp 10 accepting the applied load voltage Vload emits light. In addition, in the case where the output signal of the human body detection sensor 40 is not output for a predetermined time, the illuminating lamp control apparatus 200 blocks a load voltage Vload applied to the illuminating lamp 10. [0100]

The illuminating lamp control apparatus 200 includes a magnetic energy recovery bidirectional current switch 110, a gate phase control apparatus

220, a phase detector 130 and power supply blocking means. Power supply blocking means includes a power supply switch 310, a microcontroller 320 and a timer 330. The magnetic energy recovery bidirectional current switch 110 is brought into a series connection between the alternating power supply 20 and the illuminating lamp 10. The phase detector 130 is connected to the gate phase control apparatus 120 and is connected to a lead between the alternating power supply 20 and the magnetic energy recovery bidirectional current switch 110 and a lead between the magnetic energy recovery bidirectional current switch 110 and the illuminating lamp 10. The gate phase control apparatus 220 is connected to the human body detection sensor 40 provided in the exterior of the illuminating lamp control apparatus 200 and is connected to the magnetic energy recovery bidirectional current switch 110. The power supply switch 310 is arranged between the alternating power supply 20 and the magnetic energy recovery bidirectional current switch 110. The timer 330 is connected to the human body detection sensor 40 and the microcontroller 320. The microcontroller 320 is connected to the timer 330 and the power supply switch 310. [0101]

Components besides the gate phase control apparatus 220, the power supply blocking means and the human body detection sensor 40 are likewise in

the above described first embodiment and, therefore, detailed description thereon will be omitted here. [0102]

The gate phase control apparatus 220 is connected to the human body detection sensor 40 as described above. The gate phase control apparatus 220 serves likewise the gate phase control apparatus 120 of the first embodiment, but the signal input for controlling is different. That is, the gate phase control apparatus 120 of the first embodiment operates with output signals from the under switch 30. However, the gate phase control apparatus 220 of the present embodiment operates with output signals from the human body detection sensor 40. [0103]

The power supply blocking means includes, as described above, a power supply switch 310, a microcontroller 320 and a timer 330. The timer 330 is, as described above, connected to a human body detection sensor 40 and emits a signal to the microcontroller 320 unless an output signal from the human body detection sensor 40 is inputted for a predetermined time T3. The microcontroller 320 occasionally receives the relevant signal and then outputs power supply blocking signal to the power supply switch 310. In addition, the power supply switch 310 is, as described above, arranged between the alternating power supply 20 and the magnetic energy recovery bidirectional current switch 110.

The power supply switch 310 in receipt of the power supply blocking signal is put OFF and blocks the connection between the alternating power supply 20 and the magnetic energy recovery bidirectional current switch 110 to stop supply of the power supply voltage V to the magnetic energy recovery bidirectional current switch 110. Consequently, the load voltage Vload to the illuminating lamp 10 is blocked . [0104]

In addition, in receipt of an output signal of the human body detection sensor 40 in the state of blocking the power supply voltage V, the timer 330 supplies the microcontroller 320 with a predetermined signal. In receipt of the relevant signal of in the state of blocking the power supply voltage V, the microcontroller 320 supplies the power supply switch 310 with a power supply starting signal. The power supply switch 310 in receipt of the power supply starting signal is put ON to link the alternating power supply 20 to the magnetic energy recovery bidirectional current switch 110 link so as to resume supply of the power supply voltage V to the magnetic energy recovery bidirectional current switch 110. Consequently, the load voltage Vload is supplied to the illuminating lamp 10. [0105]

The human body detection sensor 40 is an object detection sensor detecting presence of an object

within an illumination range of the illuminating lamp 10. The object will be described as a human below. However, the object will not be limited to a human, but can be an automobile and luggage, for example. In addition, the object detection sensor is being generally used in apparatuses detecting optical changes and apparatuses detecting infrared lights and, therefore, detailed description thereon will be omitted . [0106]

The human body detection sensor 40 detects presence of a human within an illumination range. The human body detection sensor 40 having detected presence of a human outputs a predetermined output signal to the gate phase control apparatus 220 and the power supply blocking means. In addition, the human body detection sensor 40 blocks the output signal to the gate phase control apparatus 220 in the case where no human is present within an illumination range . [0107]

The gate phase control apparatus 220 in receipt of the output signal from the human body detection sensor 40 sets a gate phase angle to a reference angle αO (140°, for example) to output a control signal to the magnetic energy recovery bidirectional current switch 110 likewise the operations of the gate phase control apparatus 120 of the first embodiment in receipt of the output signal from the

user switch 30. In addition, the gate phase control apparatus 220 in receipt of no output signal sets a gate phase angle to an light-out angle αl (180°, for example) to output a control signal to the magnetic energy recovery bidirectional current switch 110. That control signal, the operations of the magnetic energy recovery bidirectional current switch 110 and the load voltage Vload output from the magnetic energy recovery bidirectional current switch 110 are likewise in the case of the first embodiment and, therefore, detailed description thereon will be omitted here.

[0108]

In addition, in the case where the above described configuration allows no output signal from the human body detection sensor 40 to be inputted for a predetermined time T3, the power supply blocking means blocks the power supply voltage V from the alternating power supply 20 to the magnetic energy recovery bidirectional current switch 110. In addition, the power supply blocking means in receipt of the output signal from the human body detection sensor 40 in a state of blocking the power supply voltage V resumes supply of the power supply voltage V from the alternating power supply 20 to the magnetic energy recovery bidirectional current switch 110.

[0109]

The timer 330 receives the above described

predetermined signal being emitted by the human body detection sensor 40 in the case where the human body detection sensor 40 detects presence of a human. In addition, the timer 330 outputs a signal to the microcontroller 320 if the relevant signal is not input for not less than a predetermined time. The microcontroller 320 receives a signal from the timer 330 and then outputs a power supply blocking signal to the power supply switch 310. The power supply switch 310 in receipt of the power supply blocking signal is put OFF to block power supply from the alternating power supply 20. Here, the predetermined time T3 can be set arbitrarily. For example, the predetermined time T3 can be half a day, one day and even around two days .

[0110]

So far, the configuration of the illuminating lamp control apparatus 200 related to the second embodiment has been described. With reference to Fig. 9, the change in the load voltage Vload in the case where the human body detection sensor 40 detects presence of a human to emit an output signal and in the case where the human body detection sensor 40 does not detect a human to emit no output signal will be described below.

[0111]

(Changes in Load Voltage Vload due to Detection State of Human Body Detection Sensor 40)

Fig. 9 is a drive waveform plane representing the

drive of the illuminating lamp control apparatus 200 related to the present embodiment. In Fig. 9, the upper diagram is a timing chart illustrating the case where the human body detection sensor 40 detects presence of a human and the case where the human body detection sensor 40 detects no human. In addition, the lower diagram is a voltage chart illustrating changes in the load voltage Vload corresponding with the detection state of the human body detection sensor 40. Here, in both charts, the horizontal axis designates time axis. However, an arbitrary time point (for example, k5) on the time axis of one chart is taken as the same time point as the corresponding time point (k5) on the time axis in the other chart. [0112]

As illustrated in the upper chart in Fig. 9, from the time point 0 until the time point k5, the human body detection sensor 40 detects presence of a human. In response, the load voltage Vload is set to a lighting voltage. Therefore, from the time point 0 until the time point k5, a lighting voltage is continuously applied to the illuminating lamp 10. In addition, from the time point k5 until the time point kβ, the human body detection sensor 40 detects no presence of a human. In response, the load voltage Vload is set to a low voltage. Therefore, for the time Tl from the time point k5 until the time point kβ, a low voltage is continuously applied to the illuminating lamp 10. In addition, from the time

point k6 until the time point k7 , the human body detection sensor 40 detects presence of a human. In response, the load voltage Vload is set to a lighting voltage. Therefore, from the time point k6 until the time point k7 , a lighting voltage is continuously applied to the illuminating lamp 10. In addition, from the time point k7 until the time point k8, the human body detection sensor 40 detects no presence of a human. In response, the load voltage Vload is set to a low voltage. Therefore, for the time period T2 from the time point k7 until the time point k8 , a low voltage is continuously applied to the illuminating lamp 10. In addition, from the time point k8 until the time point k9, the human body detection sensor 40 detects presence of a human. In response, the load voltage Vload is set to a lighting voltage. Therefore, from the time point k8 until the time point k9, a lighting voltage is continuously applied to the illuminating lamp 10. [0113]

In addition, from the time point k9 until the time point kll, the human body detection sensor 40 detects no presence of a human. In response, the load voltage Vload is set to a low voltage. Therefore, for the time T3 from the time point k9 until the time point klO, a low voltage is continuously applied to the illuminating lamp 10. However, after a lapse of the predetermined time T3, the load voltage Vload applied to the illuminating

lamp 10 will drop from a low voltage to zero so that the illuminating lamp 10 will enter a non-light- emitting state, that is, a light-out state. And at the time point kll, the human body detection sensor 40 occasionally detects presence of a human and, then the load voltage Vload is set to a lighting voltage again. Therefore, after the time point kll, a lighting voltage is applied to the illuminating lamp 10.

[0114]

Next, a flow of outputting a lighting voltage from the illuminating lamp control apparatus 200 during the period when the human body detection sensor 40 detects a human, for example, from the time point 0 until the time point k5, will be described briefly. At first, the human body detection sensor 40 detects presence of a human within an illumination range. The human body detection sensor 40 having detected presence of a human outputs a predetermined output signal to the gate phase control apparatus 220 and the timer 330. The gate phase control apparatus 220 takes receipt of the relevant output signal as that lighting is selected and sets the gate phase angle α at a reference angle αO . In addition, the gate phase control apparatus 220 receives phase information from the phase detector 130. The gate phase control apparatus 120 prepares a control signal

(ON signal) from the set gate phase angle α and the phase information to supply the gates Gl to G4 of the

magnetic energy recovery bidirectional current switch 110 with the control signal. The magnetic energy recovery bidirectional current switch 110 in receipt of supply of the control signal prepares the load voltage Vload in the size of the lighting voltage (for example, 100% of the rated voltage Va) based on the power supply voltage V supplied from the alternating power supply 20. The preparation of the relevant load voltage Vload is triggered by the operations of the above described magnetic energy recovery bidirectional current switch 110. In addition, the magnetic energy recovery bidirectional current switch 110 applies a lighting voltage being the load voltage Vload to the illuminating lamp 10. Accordingly, the illuminating lamp 10 will emit light corresponding with the lighting voltage in the case where the human body detection sensor 40 has detected presence of a human, that is, in the case of using the illuminating lamp 10 (lighting) . [0115]

Next, a flow of outputting a light-out voltage from the illuminating lamp control apparatus 200 during the period when the human body detection sensor 40 detects no presence of a human, for example, a period from the time point k5 until the time point k6, will be described briefly. At first, the human body detection sensor 40 detects no presence of a human within the illumination range. The human body detection sensor 40 detecting no presence of a human

blocks the above described output signal to the gate phase control apparatus 220. The gate phase control apparatus 220 takes blocking of the output signal as that light-out is selected and sets the gate phase angle α at a light-out angle αl (for example, 180°) . In addition, the gate phase control apparatus 220 receives phase information from the phase detector 130. The gate phase control apparatus 220 prepares a control signal (ON signal) from the set gate phase angle α and the phase information to supply the gates Gl to G4 of the magnetic energy recovery bidirectional current switch 110 with the control signal. The magnetic energy recovery bidirectional current switch 110 in receipt of supply of the control signal prepares the load voltage Vload in the size of the low voltage not being zero (for example, 50% of the rated voltage Va) based on the power supply voltage V supplied from the alternating power supply 20. The preparation of the relevant load voltage Vload is triggered by the operations of the above described magnetic energy recovery bidirectional current switch 110. In addition, the magnetic energy recovery bidirectional current switch 110 applies a low voltage being the load voltage Vload to the illuminating lamp 10. Accordingly, the illuminating lamp 10 will emit light corresponding with the low voltage at a light-out time, that is, in the case of using no illuminating lamp 10 (light-out) Accordingly, the applied voltage of the illuminating

lamp 10 will not become zero even at the light-out time so that the illuminating lamp 10 will not be put out . [0116]

And, a flow of outputting a load voltage Vload from the illuminating lamp control apparatus 100 during the period in the case where the human body- detection sensor 40 detects no presence of a human for a predetermined time T3 so that the voltage applied to the illuminating lamp 10 becomes zero, that is,- a period from the time point k9 until the time point kll, will be described briefly. From the time point k9 until the time point kll, the human body detection sensor 40 detects no presence of a human and, then, the load voltage Vload is set at first to a lighting voltage (for example, 50% of the rated voltage Va) . At that occasion, the signal from the human body detection sensor 40 is not input to the timer 330, either. Accordingly, at time point klO in a lapse of the predetermined time T3, the timer 330 outputs a predetermined signal to the microcontroller 320. The microcontroller 320 in receipt of that signal outputs a power supply blocking signal to the power supply switch 310. The power supply switch 310 in receipt of that power supply blocking signal is put OFF to block the power supply voltage V from the alternating power supply 20 to the magnetic energy recovery bidirectional current switch 110. Accordingly, the load voltage Vload

applied to the illuminating lamp 10 is also blocked to become zero.

[0117]

In addition, as illustrated at the time point kll in Fig. 9, in receipt of an output signal from the human body detection sensor 40 in the state of blocking the power supply voltage V, the timer 330 supplies the microcontroller 320 with a predetermined signal. And the microcontroller 320 in receipt of supply of that output signal outputs the power supply resuming signal to the power supply switch 310. The power supply switch 310 in receipt of the power supply resuming signal is put ON so as to connect the alternating power supply 20 to the magnetic energy recovery bidirectional current switch 110. Accordingly, the power supply voltage V is applied to the magnetic energy recovery bidirectional current switch 110 and the load voltage Vload of the lighting voltage is applied to the illuminating lamp 10.

[0118]

Therefore, according to the second embodiment of the present invention, likewise advantages of the illuminating lamp control apparatus 100 related to the above described first embodiment are attainable and automatic light-out /lighting switching can be carried out since light-out /light ing is controlled by the signal from the human body detection sensor 40. In addition, the light-out takes place more reliably than light-out / lighting control by the user switch 30

in the case of no use, giving rise, therefore, higher energy saving effects. In addition, according to the present embodiment, if the human body detection sensor 40 detects no object for not less than a predetermined time, the voltage applied to the illuminating lamp 10 can be made zero. Therefore, according to the present embodiment, more electric power consumption can be saved, giving rise to high energy saving effects. In addition, in order to make the voltage applied to the illuminating lamp 10 zero, light-out and lighting will be carried out. However, the number of lighting can be decreased more than a conventional illuminating lamp. Therefore, life extension technologies can be attained. [0119]

So far, with reference to the accompanying drawings, the preferred embodiments of the present invention have been described. It goes without saying that the present invention will not be limited to examples related to the present invention. Those skilled in the art will apparently recognize that various changes and modifications can be made within the range described in the claims hereof and those changes and modification will naturally be understood to belong to the technological range of the present invention as well. [0120]

For example, in the present embodiment, the gate phase angle α and the load voltage Vload are prepared

with an output signal of the user switch 30 or an output signal of the human body detection sensor 40. However, the present invention will not be limited to such an example. For example, the gate phase angle α can be determined by both of the output signals of the user switch 30 and the human body detection sensor 40. That is, the gate phase control apparatuses 120 and 220 can receive an input of both the output signal from the user switch 30 and the output signal from the human body detection sensor 40 to carry out the above described operations so that the load voltage Vload reaches not more than the power supply voltage V if both of the output signals are not input . [0121]

In addition, in the above described embodiment, at the lighting time, the load voltage Vload is set to not less than the power supply voltage V and, at the light-out time, the load voltage Vload is set to less than the power supply voltage V. However, the present invention will not be limited to such an example. For example, luminance of the illuminating lamp 10 can be switched stepwise or continuously by switching the user switch 30. That is, the illuminating lamp 10 can undergo light control by switching the user switch 30 to set a gate phase angle α arbitrarily so that the arbitrary gate phase angle is selected.

Industrial Applicability [0122]

The present invention can realizes energy saving technologies and life extension technologies concurrently for low costs.