FIELD OF THE INVENTION The present invention relates to the field of magnetic inductors or transformers and, in particular, relates to an inductor or transformer with a permanent magnetic core or biased core technology.

BACKGROUND OF THE INVENTION Magnetic amplifiers have been well known in the art for use in power control systems. Magnetic amplifiers rely on the fact that magnetic fields or magnetic bias are created in the magnetic circuits of inductive power components so as to effect the control of current or power. It is known in the prior art to construct magnetic inductors containing an iron core, such as disclosed in U. S.

Patents 4, 103, 221 and 4, 009, 460, both to Fukui et al. However, when an inductor utilizes a ferromagnetic core for example, the core is readily capable of reaching magnetic saturation, due to DC electric current, resulting in a reduction of the inductance. To avoid these saturation problems, Fukui et al. proposes to utilize permanent magnetic cores for the inductors, with such cores producing a permanent biasing magnetic field. By doing so, the core of the inductor is less likely to suffer magnetic saturation and has an extended range of useful inductance. However, the devices as described by Fukui et al. form a solid core structure, and are thus still heavy and are not well adapted for devices where a reduction of weight is critical.

In addition, the devices of Fukui generally do not maintain a precise and steady level of flux density or saturation, throughout a wide range of DC current.

Furthermore, the device of Fukui are specifically designed for DC current applications, and do not appear to be effective in AC current applications.

In addition, magnetic devices such as transformers, chokes and inductors commonly use silicon grade steel for the magnetic core and copper or aluminum for the windings. Over the last decades, this technology has not progressed but improvements have been made in materials and processes for the constructions of such transformers. However, a need still remains for magnetic technology with reduced energy loss characteristics, reduced weight and lower cost.

A need also exists for energy efficient and cost efficient transformers which can be utilized in high power consumption circuits, such as ballasts for street lighting and arc discharge lamp applications, or circuits used in current, power control and distribution.

SUMMARY OF THE INVENTION It is a feature of the present invention to provide inductor devices which are highly energy efficient and produce low amounts of heat.

It is another feature of the present invention to provide inductor devices which are lightweight and compact.

It is a further feature of the present invention to provide an inductor device which can be used in a variety of different applications, such as a transformer, current controller, or as a power equipment protection device.

According to the above features, from a first broad aspect, the invention comprises an inductor device which includes a magnetic circuit having first and second layers of magnetic conductive material with the layers being retained in a predetermined, spaced-apart relationship with respect to one another, so as to define opposing facing surfaces and at least first and second end portions.

The first and second layers further define a gap between the layers. The inductor device further includes a first permanent magnetic piece located at a first end portion between the layers of ferromagnetic material, and a second permanent magnetic piece located at a second end portion between the layers of ferromagnetic

material. A coil surrounds each of the first and second layers of ferromagnetic material with the coil extending within the gap between the first and second permanent magnetic pieces.

According to the above features, from a second broad aspect, the innovation provides a toroidal inductor which has a first semi-circular toroidal ferromagnetic piece having first and second ends and a second semi-circular toroidal ferromagnetic piece having first and second ends. The first and second ends of the first toroidal ferromagnetic piece are arranged to face the first and second ends of the second toroidal ferromagnetic piece such that the ends of the first and second toroidal pieces are opposed and spaced apart. Permanent magnets are interposed between the ends of the toroidal ferromagnetic pieces and are integrally joined with the toroidal pieces. This device further includes a coil surrounding a portion of either the first or second toroidal piece.

According to the above features, from a third broad aspect, the invention provides a multi-phase assembly which includes first and second frames with each of the frames having a perimeter and at least one leg extending within the perimeter of each frame. The first and second frames are retained in juxtaposition with permanent magnets interposed between the first and second juxtaposed frames. A coil surrounds at least a portion of the perimeter and a portion of at least one of the legs.

BRIEF DESCRIPTION OF THE DRAWINGS The preferred embodiments of the present invention will now be described with reference to the accompanying drawings in which FIG. 1 illustrates a perspective view of the preferred magnetic core device of the present invention.

FIG. 2 illustrates geometrical parameters of the preferred magnetic core device of the present invention, which parameters are utilized in Equations 1- 3, described in the Detailed Description of the Invention.

FIG. 3 illustrates a perspective view of an alternative embodiment of the magnetic core device.

FIG. 4 illustrates a second alternative embodiment of the magnetic core device.

FIG. 5 illustrates a plot of inductance versus current for the embodiment of Fig. 1 in a flux saturated condition.

FIG. 6 illustrates a plot of inductance versus current in a circuit with two magnetic core devices placed in an"Anti-Phase"connection, where the polarities of the two core devices are opposed.

FIG. 7 illustrates a plot of current versus time in a circuit where the magnetic core devices are placed in the Anti-phase connection.

FIG. 8 illustrates a schematic circuit diagram where magnetic core devices are placed in Anti-phase connection, and which produces the current waveform shown in Fig. 7.

FIG. 9 illustrates a plot of magnetic flux density over the length of the magnetic core assembly, along the line X-Y in Fig. 1, and at zero current flow.

FIG. 10 illustrates a plot of flux density over the length of the magnetic core assembly, along line X-Y in Fig. 1, and where the current running through the coils of the circuit are creating a field which opposes the field of the permanent magnets.

FIG. 11 illustrates a hysteresis curve plotting magnetic flux density versus field strength and which further illustrates the static and dynamic operating points of a saturated magnetic core device 14 of Fig. 8.

FIG. 12 illustrates a hysteresis curve plotting magnetic flux density versus field strength and which further illustrates the static and dynamic operating points of a flux saturated magnetic core device 16 of Fig. 8.

FIG. 13 illustrates an effective hysteresis curve plotting magnetic flux density versus field strength for the combined operation of the two flux saturated magnetic core devices in Fig. 8.

Fig. 14 illustrates hysteresis curves plotting magnetic flux density versus field strength for a standard inductor, choke or transformer, wherein the magnetic core device of the present invention is operated at non-flux saturated conditions.

FIG. 15 illustrates an application of a three-phase transformer in which the operating conditions of Figure 14 are applicable.

FIG. 16 illustrates a vector diagram for showing flux vectors that would be established for an embodiment having reduced hysteresis losses.

FIG. 17 illustrates an alternate embodiment of the invention which utilizes the principles illustrated in FIG. 16.

DETAILED DESCRIPTION OF PREFERRED EMBODIMENTS Figure 1 shows a perspective view of a preferred embodiment of the permanent magnetic core device of the present invention. This device includes two coils 4, 5 wrapped around layers of magnetically-conductive steel material 2, forming a ferromagnetic core. Permanent magnetic pieces 3 are placed at opposing ends of the assembly. However, it may be desirable in certain applications to utilize only one magnet in the magnetic core device. To couple the magnetic pieces 3 to the ferromagnetic layers 2, magnetic pole pieces may be utilized in layers positioned between the magnetic pieces 3 and the ferromagnetic layers 2. The magnets 3 are placed in such a manner that their fields are additive. The coils are

positioned between the magnetic pieces 3 and the ferromagneric layers 2. The magnets 3 are placed in such a manner that thcir fields are additive. The coils are also p ! aced so that the fields produced by y Llie coils arc additive. The present device can be utilized as a transformer, inductor, choke. or in a current, limiting circuit as well. In comparison to known prior art transtormers and inductors. the device of the present invention is lighter, and has lower demonstrated hysteresis losses in AC circuit application.

Theory Supportinc Use Of Permanent Magnetic Core Device As Current Contruller The permanent magnetic core device of the present invention can also be utilized as a current controlling device, and this application can be theoretically demonstrated. Reference is made to Figure 2 which illustrates the various dimensions of the device in Figure 1. Thp. mickness of the permanent magnet 3 is designatcd by"th". The length of the permanent magnet is illustrated by "Lm". The depth dimension of the permanent magnet is "S" and the distance of the lower surface ot rhp. magnet to the lower surface uS the ferromagnetic layer 2 is designated by"P". The ferromagnetic layer 2 has a thickness"Wi". and a coil winding length "II". Accordingly, the maximum theoretical flux density of the device will be defined by : Where "Hm" is the magnetic field strength,"Npls"is the numbcr of poles."H"is the coil winding length as illustrated in Figure 2, "th" is the magnet thicl : ness illustrated in Figure 2,"Lm"is the length of the magner illustrated in

Figure 2, "µo" is the permcability of frcc space and"pr"is the permeability of the ferromagnetic cure laycrz 2.

Tf a field is applied opposing the magnets by the coils 4 and 5 of Figure 1 of turns N, and current 1, then the residual flux density in the magnets will be given by : (2) Since the flux density is the ferromagnetic core is relared ro rhe magnetic residual flux density"Br''by the ratio Lm/W, the ferromagnetic core saturation flux density can be approximated by; If the value"Bs"is greater than the value required to samrate the core Bsal, then the inductance of the permanent magnetic core assembly will be minimal. as me curre oils A, 5 of Figure 1 is increased to the point where the core de. sarnrHt. es, then rhe inductance of the permallent magnetic core w ill maximize. Thus, equation demonstrates thqt for the saturation mode of the permanent magnetic core device, this device operates as a controller of current, In AC circuits, die maximum inductance valuc will form a high impedance to current, white the minimal inductance will Curiii a tuw iliipedance to current.

Characteristics of Permanent Magnetic Core Device e Figure 5 illustrates the variations of inductance against current on the device of Figure 1 in thé magnetic flux saturated condition. As the current : changes

change in current will also increase, and thus the device will serve as a predictable controller of current.

If two of the permanent magnetic core devices of Figure 1 are joined in series together, they can produce a system which will provide excellent control over current in AC applications. Figure 8 illustrates a simple circuit diagram where two permanent magnetic core devices, such as those shown in Figure 1, are joined together with repelling poles facing each other. The transformer device in figure 15 may also be used in three phase application, whereby the characteristics shown in figure 6 would be applicable per phase. The two permanent magnetic core devices are illustrated as 14 and 16 in Figure 8, and are connected to an AC voltage source 13, a resistance load 17, and a third structure which could be, for example, a lamp or current monitoring device 15. The operating characteristics of this circuit are illustrated in Figures 6 and 7. Figure 6 illustrates changes in inductance versus current and shows the sudden increase in inductance at both negative and positive current directions. These changes in inductance translate into changes of impedance which control the current in the circuit. The actual appearance of the electrical current waveform is illustrated in Figure 7, which plots current versus time, and demonstrates that the electrical current waveform in the system of Figure 8 is nearly square. The actual"squareness"of the waveform will depend upon the geometry of the permanent magnetic core devices employed, and other geometries for the permanent magnetic core device are illustrated in Figures 3, 4 and 15, which will be discussed in more detail in a later section. Thus, the permanent magnetic core device, whether it is used alone or in a circuit with several such devices, effectively serves as a controller of current.

Figures 9 and 10 illustrate the distribution of magnetic flux across the length of the ferromagnetic core in the permanent magnetic core device of Figures 1 and 2. In Figures 9 and 10, the length dimension on the horizontal axis is the dimension H from Figure 2, shown in centimeters. The vertical axis is flux density

in Teslas. Figure 9 illustrates the condition where the core of the device is flux saturated, while Figure 10 illustrates the core of the device in a de-saturated condition. The saturated condition is created when no current flows through the device, while the desaturated condition occurs when a current opposing the magnetic field strength flows through the device.

Figures 11 and 12 illustrate the hysteresis curves which are individually created by the devices 14 and 16 respectively in Figure 8. The hysteresis curve illustrates magnetic flux density against field strength. In Figure 11, the operating point A is well into the saturation region for the core, and represents the field produced by the magnets. If the current flow in the coils aids the magnetic field of the permanent magnets, then the operating point will move towards point B. If the current flow in the coils opposes the magnetic field of the permanent magnets, then the operating point will move towards point C. Point C is in the non-saturated area of the hysteresis curve. At this point, the inductance of the permanent magnetic core device is high. In Figure 12, the operating point E represents the device 16 in its saturated condition, while points D and F show the operating point moving towards the unsaturated condition.

Figures 13 and 14 illustrate the combined hysteresis characteristics of the two permanent magnetic core devices in Figure 8, or in the alternate embodiment of Figure 15 which will be later described. The characteristics of each permanent magnetic core device are combined to produce these diagrams of effective characteristics. Figure 13 shows the combined hysteresis characteristics when the two permanent magnetic core devices are flux saturated when no current flows, while Figure 14 shows the combined characteristics in a less saturated condition. As can be readily observed from these diagrams, the combined effects of the two permanent magnetic core devices produces a hysteresis curve with an extremely narrow area. Since the area of hysteresis curve represents energy lost by the operation of the device, it can be readily seen that a circuit utilizing biased core

technology of the preferred embodiment from Figure 1 (or later described alternate embodiment of Figures 3, 4 and 15) produces energy losses that are much lower than the energy losses experienced by conventional magnetic devices. Such reductions in energy losses translate in a reduction of heat and lower operating costs when the permanent magnetic core devices are utilized in a circuit.

ALTERNATE EMBODIMENTS OF THE INVENTION Figures 3 and 4 illustrate the alternative embodiments for the permanent magnetic core device. In Figure 3, the permanent magnets 7 are aligned in a plane. Surrounding the magnets are a toroidal ferromagnetic core 6 and pole pieces 8 attached to the internal and external peripheries of the ferromagnetic core 6. A coil 9 is wrapped around the ferromagnetic core 6. Figure 4 illustrates a similar device, although this embodiment does not utilize the pole pieces, and the permanent magnets are shown at 10. In this embodiment, the permanent magnets 10 are shown in parallel planes, which are at an angle to the diametric plane of the toroid. In a further alternate embodiment (not shown) the arrangement of Figure 4 is utilized, but the permanent magnets 10 are arranged in non-parallel planes.

The embodiments of Figures 3 and 4 have been found to be ideal for use as chokes, although their application in specific circuits are not limited to chokes alone. For example, the devices of Figures 3 and 4 may also be utilized as inductors or controllers of current, or transformers.

Another alternate embodiment of the invention is presented in Figure 15. Two core assemblies 21 and 24 are placed adjacent to one another. Magnetic assemblies are composed of magnet sets 19, 20, and pole pieces 25, and these assemblies are then sandwiched between the two core structures 21 and 24. Each of the six magnetic assemblies are arranged to have opposite polarity to each adjacent magnetic assembly in both horizontal and vertical directions. However, magnetic polarity may be varied according to a given application. Each of the three

vertical limbs are enclosed by coils. This particular device is advantageous when used as a power distribution transformer, a power distribution protection device or a current limiting device. The basic theory behind this device has been described according to Figures 5, 6, 7, 11, 12, 13 and 14. An additional discovery has been made in which we have found that if the magnetic field is established in the core which is perpendicular to the magnetic field of the permanent magnets, then the hysteresis curve for such a device will also define a smaller area than what would be observed if the perpendicular magnetic field did not exist. Thus, the creation of a magnetic field in the core which is perpendicular to the field created by horizontal pairs of permanent magnets will result in a device with substantially reduced heat generation, and greater energy efficiency. The transformer device of Figure 15 may be used in three-phase applications and displays the characteristic shown in Figure 6.

As we described the usefulness of static magnetic biasing in reducing core losses in ferromagnetic materials, we have also set out the principle that the bias field may not be restricted to the conventional direction of flux flow, but may also be used in the"orthogonal direction". Our invention can be extended to AC orthogonal biasing in which further advantages are realized in the application of power transformers.

The advantages of magnetic biasing for reducing hysteresis losses have been demonstrated in FIGS 11, 12, 13 and 14, however, we have found that many ferromagnetic materials, including ferrites, can be biased in a multi- dimensional manner as demonstrated in figure 16. Figure 16 illustrates a portion of a ferromagnetic material in which several flux density vectors are imposed. The material will exhibit a maximum flux density vector in the normal direction depicted by the non-linear vector Bnorm. Another non-linear flux density vector Borth may be imposed by a magnet or by a coil, resulting in an overall non-linear flux density vector Brefs0. Although the material may have a magnetic

saturation vector of absolute value Bnorm, the imposed orthogonal vector Borth will cause a complex non-linear vector of Breso, which exceeds the saturation value.

Due to the non-linear and inter-dependant relationship of the flux vectors described above, the"box"which depicts a two and three dimensional example (Fig 16) would not in fact have straight lines, as seen in a conventional vector diagram, but would include curved lines.

The significant point of this biasing is that the effective operating flux density of a magnetic device can be raised above the normally accepted values, with the result being improved performance. Thus, the magnetic device can be constructed in a smaller size than is normally used in conventional technology.

Since the magnet can be replaced by a coil, AC biasing becomes possible, allowing an orthogonal winding which comprises part of the functional windings of the device/transformer.

FIG. 17 illustrates a practical implementation of such a device. Slots 26 provide space for the windings, but are otherwise not necessary for orthogonal operation. The device shown in figure 17 includes a core which is wrapped with orthogonal windings 27, 28. The windings 27 and 28 may consist of several windings for coupled outputs. B_norm and Borth are shown in the drawing, demonstrating orthogonal flux paths. The scaler addition of Bnorm and Borth will exceed the saturating value of flux of the material, thus exacting and emulating a transformer or magnetic device operating beyond the normal flux operating levels of the material. The net result is lower hysteresis losses and the ability to construct the effective device in smaller sizes for weight reduction.

As can be seen in figure 17, limbs 29 conduct flux between the top and bottom sections. On one set of diagonally opposite corner, flux is additive, while on the other, it is opposing. When constructing the device of figure 17, the limbs 29 are preferably formed of unequal size.

The biased magnetic core constructions described herein are not limited to the exact configurations described, but may be varied in any manner consistent with the scope of the appended claims.