Field of the Invention

This invention relates to wireless power transfer. More particularly, though not exclusively, the invention relates to a system, apparatus, and/or method which compensates for changes in reactive impedance, such as those due to misalignment between the primary and secondary magnetic couplers in an inductive power transfer system.

Background

Wireless or contactless power transfer, and more specifically inductive power transfer (IPT) technology, is now widely used in a variety of applications. An IPT system generally comprises a primary power converter which supplies an alternating current to energise a primary magnetic coupler (alternatively referred to as a coil, conductor, or pad, for example). The primary power converter and primary magnetic coupler together form the primary side of the IPT system. The secondary side of the system comprises a secondary magnetic coupler (alternatively referred to as a pick-up, coil, conductor, or pad, for example) electrically coupled to a secondary converter which may supply power to a load. For improved power transfer efficiency, the primary and secondary sides of the IPT system each generally further comprise a resonant circuit tuned to the frequency of the alternating current (or vice versa). The operating frequency usually depends on the application and can extend up to megahertz range.

The alternating current in the primary magnetic coupler creates a changing magnetic field, at least part of which passes through the secondary magnetic coupler during operation of the IPT system, inducing a voltage which is supplied to the secondary converter and thence the load. A major advantage of IPT systems, compared to traditional wired or closely-coupled power supplies, is that without the constraint of wires or a fixed mechanical coupling, the secondary side of the system is freely moveable with respect to the primary side. Such systems are therefore suited for a wide variety of applications including stationary and dynamic electric vehicle (EV) charging and powering wearable computers, for example. However, a problem arises from the relative movement of the primary and secondary coils in that the coils may become misaligned. Any such movement or misalignment results in variations in the coil inductances, which detunes the resonant circuits. This in turn leads to the converter circuits being presented with high volt-ampere (VA) loads, resulting in increased losses, instability, and reduced power throughput. Therefore, steps may be taken to compensate for the changes in inductance of the magnetic couplers enabling the IPT system to operate under tuned conditions.

A variety of circuit topologies and control methods capable of compensating for loss in performance of IPT systems due to misalignment have been proposed in the past. The majority of these technologies either employ a variable frequency switching scheme or switchable reactive elements in order to compensate for the changes in inductance. The former method is less attractive mainly as electromagnetic compatibility (EMC) standards, for example, require IPT systems to be operated within a strict frequency band, and changes in operating frequency may result in electromagnetic interference (EMI)-related issues. On the other hand, the use of switchable reactive elements, usually in the form of a series of capacitors with switches that can be switched in or out of the compensation circuit, is costly, bulky and requires a complicated controller, while compromising overall system reliability.

Object of the Invention

It is an object of the invention to provide an inductive power transfer (IPT) system and method for operation which overcome or at least ameliorate one or more disadvantages of the prior art (including, but not limited to, those outlined above), or alternatively to at least provide the public or industry with a useful alternative.

Summary of Invention

In a first aspect, the invention may broadly be said to consist in a wireless power transfer apparatus suitable for magnetic coupling with a second apparatus, the wireless power transfer apparatus comprising:

a power converter electrically coupled or coupleable with a power source or load; a resonant circuit electrically coupled with the power converter and comprising a magnetic coupler for magnetic coupling with the second apparatus; and

a controller associated with the power converter and configured to vary a relative phase of operation of the power converter with respect to the second apparatus, the phase being varied to at least partially compensate for variations in a resonant frequency of the resonant circuit.

In one embodiment the relative phase is varied to control a reactive impedance of the resonant circuit.

More particularly, though not exclusively, the phase is varied to at least partially compensate for variations in an inductance of the magnetic coupler. Alternatively, or additionally, the phase may be varied to at least partially compensate for variations in a capacitance of the resonant circuit, and more particularly degradation of a tuning capacitor.

Variations in the inductance of the magnetic coupler may be caused by dynamic or static variations in the displacement or alignment between the wireless power transfer apparatus and the second apparatus, in use. The apparatus may comprise either a primary or secondary side of an inductive power transfer (IPT) system.

Preferably the relative phase is varied to substantially compensate for variations in the inductance of the magnetic coupler to maintain unity power factor.

Preferably the controller is further configured to vary a duty cycle of the power converter to control, and more preferably regulate, a magnitude of wireless power transfer. The power transfer may be to or from the wireless power transfer apparatus to the second wireless power transfer apparatus, or vice versa.

Preferably the power converter is controlled by the controller to generate a three-level modified square wave with a variable duty cycle. More particularly, the controller preferably controls the power converter using phase modulation.

Preferably the power converter comprises a reversible inverter/rectifier to allow for bidirectional power transfer.

More specifically, the power converter preferably comprises four switches in a full bridge configuration, and the controller operates the four switches in pairs with each pair out of phase. Preferably the duty cycle of each switch pair may be varied from 0-50% to vary the duty cycle of the power converter. Preferably the controller varies the duty cycle of the converter by varying the phase angle over which each switch pair conducts. Alternatively, the power converter may comprise a half-bridge converter or push-pull converter.

Preferably the resonant circuit comprises an inductor-capacitor-inductor (LCL) network. Alternatively, the resonant circuit may comprise a series-tuned inductor-capacitor (LC) resonant network or a push-pull parallel-resonant converter (PPRC). In a second aspect, the invention may broadly be said to consist in a method for controlling a first wireless power transfer apparatus magnetically coupled or coupleable with a second wireless power transfer apparatus, the method comprising:

varying a relative phase of operation of the first wireless power transfer apparatus with respect to the second wireless power transfer apparatus to control a reactive impedance to at least partially compensate for variations in a resonant frequency of the resonant circuit.

In one embodiment the method includes detecting an inductance or variations in the inductance of the first wireless power transfer apparatus.

Preferably the method comprises at least partially compensating for variations in the inductance of the magnetic coupler, and more preferably substantially compensating for variations in the inductance of the magnetic coupler to maintain unity power factor.

Preferably the method further comprises varying a duty cycle of the first wireless power transfer apparatus to control a magnitude of power transfer with the second wireless power transfer apparatus. The power transfer may be to or from the second wireless power transfer.

In a third aspect, the invention may broadly be said to consist in a wireless power transfer system comprising:

a first wireless power transfer apparatus according to the first aspect of the invention; and

a second wireless power transfer apparatus magnetically coupled or coupleable with the first wireless power transfer apparatus.

The wireless power transfer system may be uni-directional or bi-directional. More specifically, the system may be configured to transfer power:

only from the first wireless power transfer apparatus to the second wireless power transfer apparatus; or

only from the second wireless power transfer apparatus to the second wireless power transfer; or

in either direction between the first wireless power transfer apparatus and the second wireless power transfer apparatus. Preferably the second wireless power transfer apparatus also comprises a wireless power transfer apparatus according to the first aspect of the invention, wherein the controller is configured to vary a relative phase of operation of the power converter with respect to the first wireless power transfer apparatus. Alternatively, however, the second wireless power transfer apparatus need not necessarily comprise a controller associated with a power converter and configured to vary a relative phase of operation of the power converter with respect to the first apparatus.

Preferably the first and second wireless power transfer apparatuses each comprise a bi- directional power converter, and in particular a reversible rectifier/inverter, to allow for bidirectional power transfer.

Alternatively, the second wireless power transfer apparatus may comprise a passive diode bridge rectifier.

In a fourth aspect, the invention may broadly be said to consist in a wireless power transfer system comprising:

a primary wireless power transfer apparatus comprising:

a primary power converter electrically coupled or coupleable with a power source or load;

a primary resonant circuit electrically coupled with the primary power converter and comprising a primary magnetic coupler; and

a primary controller associated with the primary power converter to control operation thereof; and

a secondary wireless power transfer apparatus comprising:

a secondary resonant circuit comprising a secondary magnetic coupler for magnetic coupling with the primary magnetic coupler;

a secondary power converter electrically coupled with the secondary power converter and coupled or coupleable with a power source or load; and a secondary controller associated with the secondary power converter to control operation thereof,

wherein at least one of the primary and secondary controllers is operable to vary a relative phase angle between the primary and secondary wireless power transfer apparatuses to at least partially compensate for variations in a resonant frequency of at least one of the primary and secondary resonant circuits. In a fifth aspect, the invention may broadly be said to consist in a method for controlling a wireless power transfer system comprising primary and secondary wireless power transfer apparatuses, the method comprising:

detecting an inductance or variations in the inductance of a magnetic coupler of at least one of the primary and secondary wireless power transfer apparatuses; and

varying a relative phase of operation of the primary and secondary wireless power transfer apparatuses to control a reactive impedance to at least partially compensate for variations in coupler resonant frequency of at least one of at least one of the primary and secondary wireless power transfer apparatuses.

Preferably the method comprises at least partially compensating for variations in the inductance of at least one of the primary and secondary magnetic couplers, and more preferably substantially compensating for variations in the inductance of at least one of the primary and secondary magnetic couplers to maintain unity power factor and/or improve efficiency.

Preferably the method further comprises varying a duty cycle of at least one of the primary and secondary wireless power transfer apparatuses to control a magnitude of power transfer therebetween.

In another aspect the invention provides a wireless power transfer apparatus suitable for magnetic coupling with a second apparatus, the wireless power transfer apparatus comprising:

a power converter electrically coupled or coupleable with a power source or load; a resonant circuit electrically coupled with the power converter and comprising a magnetic coupler for magnetic coupling with the second apparatus; and

a controller associated with the power converter and configured to vary a relative phase of operation of the power converter with respect to the second apparatus, the phase being varied to at least partially compensate for variations in a reactive impedance.

In another aspect the invention provides a method for controlling a first wireless power transfer apparatus magnetically coupled or coupleable with a second wireless power transfer apparatus, the method comprising:

varying a relative phase of operation of the first wireless power transfer apparatus with respect to the second wireless power transfer apparatus to control a reactive impedance to at least partially compensate for variations in a reactive impedance seen by a converter of the first wireless power transfer apparatus.

Further aspects of the invention, which should be considered in all its novel aspects, will become apparent from the following description.

Drawing Description

A number of embodiments of the invention will now be described by way of example with reference to the drawings in which:

Fig. 1 is a schematic diagram of a first embodiment of an inductive power transfer (IPT) system according to the present invention;

Fig. 2 illustrates example primary and secondary voltage waveforms according to the embodiment of Fig. 1 ;

Fig. 3 is an equivalent circuit model of the system of Fig. 1 ;

Fig. 4 is a block diagram of a possible controller according to the present invention, which is suitable for use in the system of Fig. 1 ;

Fig. 5 show graphs of both compensated and uncompensated (a) input impedance and (b) angle versus frequency;

Fig. 6 shows (a) uncompensated and (b) compensated voltage and current waveforms of the embodiment of Fig. 1 ;

Fig. 7 is a graph of system efficiency of the embodiment of Fig. 1 , with and without the compensation provided by the present invention;

Fig. 8 shows (a) uncompensated and (b) compensated voltage and current waveforms of an alternative embodiment of an IPT system according to the present invention; and

Fig. 9 shows (a) uncompensated and (b) compensated voltage and current waveforms of yet another embodiment of the invention.

Detailed Description of the Drawings

The present invention comprises a wireless power transfer apparatus and system, and methods for controlling the same. Throughout the description like reference numerals will be used to refer to like features in different embodiments.

Figure 1 schematically illustrates a bi-directional inductive power transfer (IPT) system 100 substantially as disclosed by International Patent Publication No. WO 2010/062198, the content of which is incorporated herein in its entirety. The example IPT system comprises a primary side 1 10 and a secondary side 120, in this example each electrically substantially identical. The primary side comprises a primary controller 1 1 1 which controls operation of the primary converter 1 12 comprising four switches in a full bridge circuit configuration. The primary converter is coupled to the primary power source/sink, V _in , and a resonant circuit 1 1 3. The resonant circuit 1 13 in this example comprises a tuned inductor-capacitor-inductor (LCL) circuit made up of series inductor L _pi , tuning capacitor C _pt , and primary magnetic coupler L _pt .

The secondary side 1 20 of the IPT system 1 1 1 similarly comprises a secondary controller 121 , secondary converter 122, and LCL resonant circuit 1 23 comprising a secondary magnetic coupler L _st . The magnetic or inductive coupling between the primary and secondary magnetic couplers L _pt , L _st is represented by the mutual inductance M and voltage sources l/ _p; and Ir respectively.

As disclosed in WO 2010/0621 98, the primary controller 1 1 1 preferably drives the switches of the primary converter 1 1 2 in pairs at a fixed frequency f _T (preferably equal to the designed resonant frequency of the resonant circuit 1 1 3) to produce a voltage waveform V _pi as shown by way of example in Fig. 2. In this example, the voltage waveform comprises a three-level modified square wave. The phase angle φ _ρ over which each pair of switches in the primary converter 1 1 2 (in this case, functioning as an inverter) remains switched on may be varied (between 0° and 180°), thereby determining the duty cycle (ψρ/(π- φ _ρ )) of the converter to control the magnitude of the alternating current l _pi supplied to the primary magnetic coupler, Lpt. Similarly, the phase angle φ _Ξ over which each pair of switches in the secondary converter 1 22 (in this case, functioning as rectifier) remains switched on may be varied (between 0° and 1 80°), thereby determining the duty cycle (φ^ττ- φ ₅ )) of the converter.

Referring still to Fig. 1 and Fig. 2, the secondary converter 122 is controlled by the pick- up/secondary controller 1 21 similarly to the primary converter 1 12 to produce a secondary voltage waveform V _SI with controllable duty cycle. Wireless power transfer takes place across an air-gap between primary and pick-up magnetic couplers L _pt , L _st which are loosely coupled to each other through mutual inductance M. When power is transferred from the primary side to the secondary side of the system, the secondary converter 1 22 functions as a rectifier. However, as in this example at least some embodiments of the invention are capable of transferring power in either direction between the primary and secondary sides. In such bi-directional embodiments, the primary converter 1 1 2 and secondary converter 1 22 thus preferably each comprise an active reversible rectifier/inverter. The term "converter" as used throughout the description is therefore intended to encompass a rectifier (whether passive or active), an inverter, or a reversible inverter/rectifier, the appropriate selection of which is dependent on the application. The relative phase angle Θ and/or converter phase angles φ _ρ , φ _Ξ may be varied to control the magnitude and direction of power flow between the primary and secondary sides of the IPT system (dependent on the power requirements of the load coupled with the secondary side, for example). Often, the relative phase angle Θ may be fixed or regulated at ±90° for unity power factor operation, while the magnitude of power transfer is controlled by varying the converter phase angles φ _ρ , φ _Ξ . Alternatively, all three phase angles θ, φ _ρ , φ _Ξ may be varied to control the magnitude and direction of power flow. According to the present invention, however, the relative phase angle Θ is varied to control a compensating reactive impedance in order to compensate for any variation in reactance and thus maintain the tuning of both the primary and secondary magnetic couplers L _pt , L _st . The secondary output power V _out is thus regulated independently of the amount of compensation applied to maintain the tuned condition.

To further explain the theory and operation of the present invention, a mathematical analysis of the IPT system of Fig. 1 is presented below.

The example IPT system shown in Fig. 1 employs identical electronics on both the primary and secondary side, each comprising a full-bridge converter and an LCL resonant network tuned to the fundamental frequency f _T oi V _pi as given by Equation (1 ).

1 1 1 1

( _{1 )}

^pt°pi ^ρί °ρί ^Si °St ^si °si

To simplify the analysis, the voltage V _pi produced by the primary converter 1 12 can be represented by an equivalent sinusoidal voltage source that has a frequency ^ and a phasor- domain magnitude as given by Equation (2).

, _pt = ¾in (¾ 0 (2)

Similarly, the voltage produced by the secondary converter is given in the phasor-domain by Equation (3).

. (<Pp\ _{/ 0} i \

V _si = sin — ) Δθ (3) At steady state, the voltage V _sr induced in the secondary magnetic coupler L _st due to current Ipt is given by Equation (4).

V _sr = ja)MI _pt (4) Similarly, the voltage V _pr reflected back into or induced in L _pt due to current / _s; in L _st can be expressed by Equation (5).

V _pr = j6oMI _st (5)

Under tuned conditions in Equation (1 ), the currents l _pi , l _pt , / _s , and / _s; can therefore be derived as given by Equations (6)-(9).

M

>T ^L pt ^L 'st OJ _T L _pt

M

>T ^L pt ^L 'st

Ml

Ist = -j— _r V _st (9)

The IPT system of Fig. 1 can thus be represented by the equivalent circuit model shown in Fig. 3, where the induced voltage sources V _pr, V _sr are represented by complex impedances Z _pr , Z _sr , respectively. Using Equations (2)-(9), the complex impedances Z _pr and Z _sr can be derived as given by Equations (10) and (1 1 ). o) _T ML _pt sinQ s) . o) _T ML _pt sin(y _s )

Zpr = ; . ₍ sin(f?) + j— . _f . cos(f?) = R _pr + jX _pr 10

L _st s ( (p _p ) Lst sm((p _p )

Z _sr = = R _sr + jX _sr 1 1

Lpt sin <ppj Lp _t sin (^pj

As evident from Equations (10) and (1 1 ), both Z _pr and Z _sr comprise a resistive component R _sr respectively) and a reactive component (X _pr , X _sr respectively). The resistive components in Z _pr and Z _sr represent the real power transferred between the primary and the secondary sides of the system. The magnitudes of R _pr and R _sr can be controlled through φ _ρ , <Ps and Θ to regulate the amount and direction of power flow as discussed previously. The reactive components, X _pr and X _sr , do not contribute towards real power flow. In IPT systems of the prior art, the reactive components are eliminated by operating the IPT system with a fixed relative phase difference Θ of ±90°.

According to the present invention, the reactive components X _pr , X _sr are, in effect, used to compensate for the changes in the resonant frequency of the primary and/or secondary resonant circuits. For example, variations in the inductance of the primary and secondary magnetic couplers L _pt , L _st may be caused by static or dynamic variations in displacement or alignment therebetween. The converter phases φ _ρ , <p _s or duty cycle in each of the primary and secondary side of the IPT system are controlled to regulate the magnitudes of resistive components R _pr, R _sr of the impedances Z _pr , Z _sr and therefore the power transfer, whereas the relative phase difference Θ is controlled to regulate the magnitudes of reactive components X _pr, X _sr \o negate changes in reactive impedance. Such changes in reactive impedance may affect the resonant frequency of the resonat compensation networks and thus prevent efficient power transfer. The variations in reactive impedance may be due to a variety of different factors, including but not limited to: changes in the inductance of the primary and/or secondary magnetic couplers L _pt , L _st possibly due to misalignment of magnetic couplers; the presence of foreign (magnetically permeable) objects near one or the magnetic couplers; variations in component tolerances, for example degradation of a capacitor over time.

As a result, the magnitude and direction of power transfer as well as the amount of compensation can be controlled independently through the phase angles φ _ρ , <p _s and Θ. For example, if the inductances of the primary and secondary magnetic couplers L _p t, L _s t decrease beyond their tuned values (i.e. the values selected for tuning the resonant circuit to the operating frequency f _T ), Θ is controlled to introduce extra inductive reactances in series with the primary and secondary magnetic couplers L _pt , L _st \o negate the decrease in inductance of the magnetic couplers. Meanwhile, the converter phase angles φ _ρ , φ _Ξ can be varied to control the magnitude and direction of power transfer at a desired level. Alternatively, a combination of φ _ρ , <p _s and Θ can also be varied, as appropriate, to meet the required power throughput as well as to compensate for any pad misalignment.

The proposed compensation can be realised by a controller on either or both of the primary or secondary/pick-up side of the IPT system which detects changes in tuning and controls one or more of φ _ρ , φ _Ξ and Θ in order to mitigate these changes. A suitable secondary controller according to one embodiment of the invention is shown in Fig. 4 by way of example. A change in inductance of, in this example, the secondary magnetic coupler L _st is evaluated using measurements of the secondary voltage V _si and current / _s . The evaluation may comprise calculation of the power P by multiplying the voltage V _si and current / _s , as shown, for example. The evaluation is then compared with 0.5 to generate an error signal. The value of 0.5 is the value expected if Θ is to be set to achieve minimum VA for the example controller shown. However, alternative values may be used if, for example, the objective is to maximise power transfer. The error signal forms an input to a control algorithm, in this case the proportional-integral controller PI. The output of the controller PI drives a voltage controlled oscillator VCO to obtain the phase angle Θ required to compensate for changes in the system. This phase-shift is used together with the reference power level P _ref \o generate drive signals controlling operation of the converter 122. The phase of the primary IPT apparatus is taken into account in the multiplication of the secondary voltage and current, as the secondary current is related to the primary phase.

The controllers 1 1 1 , 121 may be implemented purely in hardware, software, or combinations thereof. The controllers may therefore comprise a microcontroller communicatively coupled with voltage and current sensors and programmed to perform the methods of the invention as described herein by way of example. The electronic circuit design and programming techniques required for this are known to those skilled in the fields of digital electronics and/or embedded systems.

Waveforms from a simulated IPT system according to the example embodiment of Figs. 1 -4 are shown in Figs. 5-7. The simulated system comprised LCL resonant circuits tuned to 40 kHz. Figure 5 shows graphs of both compensated 50 and uncompensated 51 (a) input impedance seen by the primary converter and (b) phase angle Θ versus frequency f for a scenario where a 20% change in the inductance of both the primary and secondary magnetic couplers L _pt , L _st has been introduced. In practice, such variations in the inductance of the magnetic couplers may be due to variations in the displacement or alignment therebetween.

Ideally, the impedance seen by the primary converter should be a purely resistive load at the operating frequency to operate the system at unity power factor. The results illustrated by the solid lines indicate the behaviour of the system without any compensation whereas the results in dotted lines represent the system behaviour when the changes in the magnetic coupler inductances Lpt, Lst <¾i"s compensated by varying the relative phase angle Θ. Without compensation, variation of the magnetic coupler inductances L _p t, L _s t causes the impedance curves to shift to the left, forcing the resonant frequency to around 38 kHz. The system becomes detuned, as the primary and secondary converters continue to operate at the designed frequency of 40 kHz, while the resonant frequency of the LCL networks has shifted to 38 kHz as a result of changes in the magnetic coupler inductances L _pt , L _st .

Varying the relative phase angle Θ from 90° to 80° in accordance with the methods, apparatus, and systems of the present invention, as shown by the broken line impedance curves in Fig. 5, restores the resonant frequency of the primary and secondary LCL resonant circuits 1 13, 123 to or towards the original value of 40 kHz, and allows the system to be operated at unity power factor, or at least nearer unity power factor than would otherwise be the case.

Voltage and current waveforms V _pii l _pi waveforms obtained from the simulated IPT system with and without compensation according to the present invention are depicted in Figs. 6(a) and Fig. 6(b), respectively. As evident from Fig. 6(a), the current / _p , is lagging the voltage V _pi , indicating that the system is operating under detuned conditions without the compensation of the present invention. Furthermore, it can be observed that the instantaneous power supplied by the primary converter 1 12 has a negative portion indicating operation below unity power factor. Referring to the compensated waveforms of Fig. 6(b), however, it can be observed that the voltage V _pi and current l _pi are in phase and the system operates at unity power factor.

The efficiency of the simulated system versus magnetic coupler inductance, with and without the proposed compensation of the present invention, is shown in Fig. 7. It can be observed that the compensation technique significantly improves the efficiency of the IPT system over a wide range of primary and secondary magnetic coupler inductances L _pt , L _st .

The above example embodiment of the invention comprises a bi-directional IPT system with a full bridge active reversible rectifier/inverter and LCL resonant circuits on both the primary and secondary sides, however the invention is not limited to such a configuration. In other embodiments, the IPT system may comprise a uni-directional (i.e. configured to transfer power in a single direction from the primary to the secondary side) system, an alternative active or passive converter such as a half-bridge or push-pull converter or passive (diode bridge) rectifier, and/or an alternative resonant circuit topology. In some embodiments of IPT systems according to the present invention, specifically unidirectional embodiments, the secondary converter may comprise a passive diode bridge rectifier and omit the secondary controller for cost or complexity reasons. The passive rectifier limits the controllability of the magnitude of compensating reactive impedance, but the compensating impedance can still be controlled to some extent by the primary controller and primary converter, at the expense of load regulation at the output of the secondary side.

In yet other embodiments, the resonant circuit may comprise a series-tuned LC resonant network or a push-pull parallel-resonant converter (PPRC), for example. Simulated waveforms for each of these embodiments are shown in Figs. 8 and 9, respectively. Figures 8(a) and 8(b) respectively show the uncompensated and compensated voltage V _ph current l _pi , and instantaneous power waveforms for a series-tuned LC resonant network embodiment. Figures 9(a) and 9(b) similarly show the respective uncompensated and compensated voltage V _pi and current / _p , waveforms for the PPRC-based embodiment. In both cases it can be observed that the compensation of the present invention restores the voltage V _pi and current l _pi waveforms to being substantially in phase with each other, resulting in an improved power factor and facilitating zero-voltage switching (ZVS).

In other embodiments, regulation of the output voltage or current may not be required, and the controllers thus need not necessarily be configured to vary the duty cycle of the power converter.

In yet other embodiments, the relative phase angle between the primary and secondary sides may be varied to control, at least in part, the magnitude of real power transfer. This may involve a compromise between controlling the magnitude of power transfer and compensating for variations in the resonant frequency of the primary and/or secondary resonant circuit. The appropriate balance will depend upon the application.

The above variations are described merely as non-limiting examples. Further modifications or variations may be made without departing from the spirit or scope of the invention.

Although the invention has been described by way of example and with reference to possible embodiments thereof, it is to be understood that modifications or improvements may be made thereto without departing from the scope of the invention. The invention may also be said broadly to consist in the parts, elements and features referred to or indicated in the specification of the application, individually or collectively, in any or all combinations of two or more of said parts, elements or features. Furthermore, where reference has been made to specific components or integers of the invention having known equivalents, then such equivalents are herein incorporated as if individually set forth.

From the foregoing it will be seen that a wireless power transfer apparatus, system, and method is provided which effectively compensates for changes in inductance arising from variations in the displacement or alignment of primary and secondary magnetic couplers.

The compensation results in improved power factor and efficiency of wireless power transfer.

This advantage can be achieved without varying the switching frequency or adding switchable reactive elements and, in at least some embodiments, without compromising load/output regulation.

Unless the context clearly requires otherwise, throughout the description, the words "comprise", "comprising", and the like, are to be construed in an inclusive sense that is to say, in the sense of "including, but not limited to", as opposed to an exclusive or exhaustive sense.

Any discussion of the prior art throughout the specification should in no way be considered as an admission that such prior art is widely known or forms part of common general knowledge in the field.