Background of the Invention In a typical RFID, a transceiver transmits a carrier reference signal which is picked up by the antenna of a tag circuit. The carrier signal powers up the tag circuit which generates an amplitude modulated data and/or identification signal which is picked up by the transceiver antenna and processed by receiver circuits in the transceiver. Due to various factors such as component tolerances, sampling of the modulated carrier signal by the reference signal is difficult to optimize because the ideal amplitude modulation can be converted to a combination of amplitude and phase modulation or, in extreme cases, to purely phase modulation.

Prior Art Various techniques have been used to solve the problem including envelope detection, I/Q detection and AST (Adaptive Sampling Time). Each of the known techniques has one or more disadvantages ranging from performance degradation to requiring a microprocessor controlled feedback loop.

Philips Semiconductors Application Note AN97070, pg. 24-30, describes the AST technique. This reference teaches that data may be recovered from the modulated carrier signal even though the signal is phase and/or amplitude modulated provided the modulated carrier signal is sampled at an optimum time 2x where x is the measured phase angle between the carrier reference signal and the modulated carrier signal subtracted from the ideal phase angle.

Summary of the Invention An object of the present invention is to provide a radio frequency identification device wherein a tag reader transmits a radio frequency carrier reference signal and a tag circuit modulates the reference signal to produce a modulated data signal that is returned to the tag reader, the tag reader being characterized in that it comprises: a delay locked loop for producing a sampling signal that is phase locked to the reference signal ; detector means for detecting a phase difference between the reference signal and the data signal ; and, means responsive to the detector means for injecting an offset signal into the delay locked loop whereby the sampling signal is phase locked to the reference signal with a phase difference that is twice the detected phase difference between the reference signal and the data signal.

In a preferred embodiment, the detector means comprises a dual edge phase detectorwhich measures the difference in phase between both the leading edges of the reference and data signals and the trailing edges of these signals, and produces two pulses having a total duration proportional to twice the phase difference.

Another object of the invention is to provide a radio frequency identification device as described above wherein the means for injecting an offset signal into the delay locked loop comprises current generators for charging a filter capacitor in the delay locked loop, the current generators being connected to the capacitor via switches controlled by output pulses from the dual edge phase detector. A positive current generator is connected to the capacitorwhen the reference signal leads the data signal and a negative current generator is connected to the capacitor when the data signal leads the reference signal.

A further object of the invention is to provide a radio frequency identification device as described above wherein the voltage on the capacitor controls the delay imparted to the reference signal to produce the sampling signal. The delay locked loop includes a further phase detector for producing an output signal proportional to the difference in phase between the sampling and reference signals. The output signal from the further phase detector controls switches which connect a positive current generator to the filter capacitor when the sampling signal leads the reference signal, or connect a negative current generator to the capacitor when the reference signal leads the sampling signal.

The delay locked loop may be implemented with plural delay elements thus permitting I/Q demodulation of the modulated data signal returned to the tag reader.

Other objects and advantages of the invention will become evident upon consideration of the following description and the accompanying drawings.

Brief Description of the Drawings Fig. 1 is a schematic diagram illustrating the basis components of a radio frequency identification system; Fig. 2 is a block diagram showing the components of a control loop according to the invention; Fig. 3 shows details of the dual edge phase detector of Fig. 2; Fig. 4 illustrates details of the phase detector shown in Fig. 2; Fig. 5 illustrates details of the offset charge pump and loop filter shown in Fig. 2; Fig. 6 shows details of the controllable delay circuit of Fig. 2; and, Fig. 7 is a timing diagram illustrating the timing of various signals in the control loop of Fig. 2.

Detailed Description of the Invention Fig. 1 illustrates a typical RFID 10 comprising a tag circuit 12 having an antenna 14 and a transceiver illustrated as an oscillator 16, an antenna 18 and a receiver 20. Oscillator 16 generates a radio frequency carrier reference signal which is applied to antenna 18. Antenna 18 generates an RF electromagnetic field 24 which is picked up by the tag circuit antenna 14 of any tag circuit 12 brought within the RF field. The carrier signal provides power for tag circuit 12 and the tag circuit amplitude modulates the carrier signal in a known manner to produce a data signal that is returned to receiver 20 via antennas 14 and 18.

Component tolerances and other factors may convert the amplitude modulation to phase modulation so that the data signal is shifted in phase relative to the carrier reference signal by some angle x. According to the invention, the receiver 20 is provided with a control loop 30 (Fig. 2) which effectively determines x and produces a sampling signal (DLYOUT) that is delayed by 2x relative to the carrier reference signal. The sampling signal may then be utilized in the receiver 20 to sample the data signal returned from tag circuit 12 at the optimum time.

Control loop 30 comprises a dual edge phase detector 32, a phase detector 34, an offset charge pump 36, a loop filter 38 and a controllable delay (DLY) 40. The carrier reference signal from oscillator 16 is squared by a signal shaper 22 (Fig. 1) to produce the signal REF which is applied to a B input of dual edge phase detector 32, an A input of phase detector 34, and a first input of DLY 40. The data signal returned to receiver 20 is amplified by an amplifier 26 and squared by a signal shaper 28 to produce the signal DATA which is applied to an A input of dual edge phase detector 32.

The dual edge phase detector 32 detects zero axis crossings of the signals REF and DATA and produces a signal UPA if REF leads DATA or a signal DOWNA if DATA leads REF. Referring to Fig. 3, the dual edge phase detector 32 comprises four D-flip-flops, 42,44,46 and 48, two inverters 50 and 52, two NANDs 54 and 56, and two Or circuits 58 and 60.

The signal REF is applied to FF42 and is inverted by inverter 50 before being applied to FF46. The signal DATA is applied to FF44 and is inverted by inverter 52 before being applied to FF48. The output of FF42 is the signal UP1 which is applied to Or 58 and a first input of NAND 54. The output of FF44 is the signal DOWN1 which is applied to Or 60 and a second input of NAND 54. In like manner, the output of FF46 is the signal UP2 that is applied to Or 58 and a first input of NAND 56, and the output of FF48 is the signal DOWN2 applied to Or 60 and a second input of NAND 56. The output of NAND 54 is connected to the reset input of FF42 and FF44 while the output of NAND 56 is connected to the reset input of FF46 and FF48.

Referring to Figs. 3 and 7, and assuming that the signal REF leads the signal DATA, the dual edge phase detector 32 operates as follows. When the signal REF crosses the zero axis in the positive direction it sets FF42 thus generating the signal UP1 to enable one input of NAND 54. The signal UP1 passes through Or 58 to become the signal UPA. This signal is applied to an electronic switch 70 (Fig. 5) in the offset charge pump 36.

When the signal Data crosses the zero axis in the positive direction it sets FF44 thus producing the signal DOWN1. This signal passes through Or 60 to become the signal DOWNA (not shown in Fig. 7) that is applied to an electronic switch 72 (Fig. 5) in the offset charge pump 36. The signal DOWN A persists only momentarily. As soon as FF44 is set, its output signal enables the second input of NAND 54 and the output of the NAND resets FF42 and FF44 thus terminating both UPA and DOWNA.

When the signal REF crosses the zero axis in the negative direction the output of inverter 50 sets FF46 thus generating the signal UP2 to enable one input of NAND 56. The signal UP2 passes through Or 58 to become the signal UPA which is applied to electronic switch 70 in the offset charge pump 36.

When the signal Data crosses the zero axis in the negative direction it sets FF48 thus producing the signal DOWN2. This signal passes through Or 60 to become the signal DOWNA that is applied to electronic switch 72 in the offset charge pump 36. Again, the signal DOWNA persists only momentarily. As soon as FF48 is set, its output signal enables the second input of NAND 56 and the output of the NAND resets FF46 and FF48 thus terminating both UPA and DOWNA.

From the preceding description it is seen that FF42 and FF44 detect the leading edges of the signals REF and DATA, respectively, and produce the signal UPA having a duration proportional to the error or difference in phase between the leading edges of the two signals. In like manner, FF46 and FF48 detect the trailing edges of the signals REF and DATA, respectively, and again produce the signal UPA proportional to the difference in phase between the trailing edges of the two signals. Thus, over one cycle the duration of UPA is proportional to twice the phase error between the signals REF and DATA.

When the signal DATA leads the signal REF, detector 32 produces two pulses of the signal DOWNA, the total duration of the two pulses being proportional to twice the difference in phase between the signals DATA and REF.

In this case, zero axis crossings of the signal DATA set either FF44 (for positive- going crossings) or FF48 (for negative-going crossings) to produce the signal DOWNA. The signal DOWNA is terminated when FF42 or FF46 is set by the signal REF since the setting of FF42 causes NAND 54 to reset both FF42 and FF44 and the setting of FF46 causes NAND 56 to reset FF46 and FF48.

As shown in Fig. 4, the phase detector 34 comprises two D-flip-flops 62 and 64 having outputs connected to a NAND 66. Phase detector 34 detects the difference in phase between the leading edges of the signal REF and the control loop feedback signal DLYOUT derived from controllable delay 40 as subsequently described. If the signal DLYOUT leads the signal REF then FF62 is set as DLYOUT goes positive. FF62 produces the signal UPB which is applied to an electronic switch 74 (Fig. 5) in offset charge pump 36. Subsequently, when the signal REF goes positive it enables NAND 66 and the output of the NAND resets both FF62 and FF64 thus terminating the signal UPB.

If the signal REF leads the signal DLYOUT then REF sets FF64 first to produce the signal DOWNB and this signal is applied to an electronic switch 76 in the offset charge pump 36. DOWNB is terminated when the signal DLYOUT goes positive to set FF62, and then, through NAND 66, reset both FF62 and FF64.

As shown in Fig. 5, the offset charge pump 36 comprises the electronic switches 70,72,74 and 76, previously mentioned, and a current generating means illustrated as two positive current generators 78 and 80, and two negative current generators 82 and 84. Positive current generators 78 and 80 are connected to the offset pump output line 86 through electronic switches 70 and 74, respectively whereas the negative current generators 82 and 84 are connected to the output line 86 via electronic switches 72 and 76, respectively.

The output lead 86 of the offset charge pump is connected via loop filter 36 to four current generators 88 (Fig. 6) in the controllable delay circuit 40. The controllable delay circuit 40 further comprises four controllable delay amplifiers 90 connected in series, the signal REF being applied to the first amplifier in the series. The output of the last amplifier in the series is the signal DLYOUT which is applied to phase detector 34 and is also used in receiver circuits 20 to sample the signal DATA to recover the data from the modulated carrier signal transmitted by tag circuit 12.

The controllable delay circuit 40 need not be implemented as shown. Any form of controllable delay elements may be used. The delay circuit 40 may also be implemented as a single controllable delay. However, a delay circuit comprising four controllable delay elements permits quadrature (I/Q) detection of the input signal. The signal DELAYOUT90DEG at the output of the next to last delay amplifier leads the signal DELAYOUT by 90 degrees. These two signals may be applied to an l/Q demodulator (not shown) in receiver circuits 20 for I/Q detection of the data.

Phase detector 34, offset charge pump 36, filter 38 and controllable delay 40 comprise a delay locked loop which, in the absence of signals from dual edge phase detector 32, produces the signal DLYOUT that is in phase with the signal REF. If the signal REF should shift in phase so as to lead the signal DLYOUT, phase detector 32 produces the signal DOWNB to activate switch 76 (Fig. 5) and connect negative current generator 84 to the output lead 86 of the offset charge pump 36. This causes a decrease in the voltage on the capacitor of filter 38 and a corresponding decrease in the control signal DCONT applied to current generators 88 (Fig. 6). In response to a decrease in the control signal DCONT the current generators 88 increase the currents applied to delay amplifiers 90 so that the delay of the signal REF in each amplifier is decreased by one-fourth the difference in phase between the signals REF and DLYOUT as detected by phase detector 34 and the signal DLYOUT is brought into phase with the signal REF.

The bandwidth of the delay locked loop must be low to minimize jitter.

On the other hand, if phase detector 34 detects that the signal REF trails the signal DLYOUT, the detector produces the signal UPB to turn on electronic switch 74, thereby increasing the voltage on output lead 86. The resulting increase in the control signal DCONT causes a decrease in the control signals applied to delay amplifiers 90 so that the delay imparted to the signal REF by the series of delay amplifiers is increased by an amount equal to the difference in phase between the signals REF and DLYOUT as detected by phase detector 34, thus bringing the signal DLYOUT in phase with the signal REF.

The dual edge phase detector 32 and the switches 70 and 72 in the offset charge pump 36 comprise a means for injecting a phase offset into the operation of the delay locked loop so that the signal DLYOUT, instead of being locked in phase with the signal REF, is locked to the signal REF with a phase offset of 2x where x is the phase difference between the carrier reference signal REF and the modulated signal DATA returned to the reader a the tag circuit 12. The dual edge phase detector 32 detects the phase difference between the signals REF and DATA as previously described and produces one of the signals UPA or DOWNA depending on which of the signals is leading.

If the signal REF is leading the signal DATA, dual edge phase detector 32 produces the signal UPA to turn on switch 70 in the offset charge pump 36 twice during each cycle, once when the signal UP1 is produced by the difference in phase between the leading edges of the signals and once when the signal UP2 is produced by the difference in phase between the trailing edges. Switch 70 connects positive current generator 78 to the output lead 86 so that the capacitor comprising filter 38 is charged to some voltage depending on the duration of the signal UPA (the sum of the durations of signals UP1 and UP2). Thus the signal DCONT rises to a voltage representing twice the difference in phase between the signals REF and DATA. The signal DCONT controls current generators 88 to decrease the control signals applied to delay amplifiers 90 so that the series of delay amplifiers delays the signal REF by twice the difference in phase between the signal REF and DATA. Therefore, the output signal DLYOUT produced by the controllable delay 40 may be used by circuits (not shown) in receiver circuit 20 to sample the signal DATA at the optimum time.

Since the signal DLYOUT has been delayed by 2x relative to the signal REF, the phase detector 34 will produce the signal DOWNB for an interval 2x on the next cycle thereby tending to discharge filter capacitor 38 through switch 76 at the same time the first UPA pulse connects the filter capacitor to positive current generator 78 through switch 70.

It should be obvious from the foregoing description that if the signal DATA leads the signal REF on a given cycle then phase detector 34 produces the signal UPB on the next cycle, UPB having a duration of 2x.

Although the invention has been described to illustrate its principle of operation, it will be understood that various modifications and substitutions may be made in the described embodiment without departing from the spirit and scope of the invention as defined by the appended claims. For example, current generators 70 and 74 may be replaced with a single positive current generator controlled by both the signals UPA and UPB. In like manner, current generators 72 and 76 may be replaced with a single negative current controlled by the signals DOWNA and DOWNB. Other types of phase detectors and/or delay elements may be used.