REFERENCE TO RELATED APPLICATIONS

[0001] This application claims priority to and the benefit of U.S. Patent Application No. 15/192,911 filed June 24, 2016, which is incorporated herein by reference in its entirely.

TECHNICAL FIELD

[0002] This application relates generally a transmitter, and more particularly to a voltage mode driver with charge recycling.

BACKGROUND

[0003] To save power, it is conventional to transmit data using a "low-swing" differential voltage signal. The signaling is deemed to be low swing in that the differential voltage is less than the power supply voltage. For example, the power supply voltage may be IV but the differential voltage for a low-swing differential voltage signal may be 300 mV or even lower such as 240 mV. Since the low-swing differential voltage signal is not driven "full rail" to the power supply voltage, power is conserved.

[0004] To provide the reduced voltage for a low-swing differential transmitter, it is conventional to use a low-drop-out (LDO) regulator. The LDO regulator acts as a resistor such that it introduces a power loss in converting the power supply voltage to the reduced voltage used for the low-swing differential signaling. This power loss gets repeated in that it is conventional to transmit a multi-bit-wide digital word using a corresponding plurality of low-swing differential signals. Each signal draws its own current from the LDO regulator that introduces its own corresponding power loss. [0005] Accordingly, there is a need in the art for differential low-swing signaling with reduced power consumption.

SUMMARY

[0006] To provide reduced power consumption, a plurality of drivers for differential data output signals are coupled in series such that a current from a first one of the drivers is recycled through the remaining drivers. The first driver includes a pair of output nodes coupled to a plurality of transistors that act as switches to alternate a charging of the output nodes depending upon a binary state of a first differential data input signal. If the first differential data input signal has a first binary value, a first one of the output nodes is coupled to a power supply node supplying a power supply voltage whereas a remaining one of the output nodes is coupled to an intermediate voltage node charged by a power converter to an intermediate voltage that is less than the power supply voltage. If the first differential data input signal has a second binary value, the coupling is switched such that the first output node is coupled to the intermediate voltage node and the remaining output node is coupled to the power supply node.

[0007] The output nodes couple through transmission lines to a receiver to form a circuit such that output node charged to the power supply voltage drives a first current through the receiver back to output node charged to the intermediate voltage. This first current is then recycled through the remaining driver(s). For example, if there are just two drivers, the remaining second driver alternates the charging of its pair of output nodes between the intermediate voltage and ground. Just like the first driver, the second driver includes a plurality of transistors that function as switches in response to a second differential data input signal to selectively couple the second driver's output nodes to intermediate voltage node and ground. The first current from the first driver is thus recycled as a second

2 current in the second driver that is sourced from the output node coupled to the intermediate voltage node and conducted into ground by the remaining output node coupled to ground.

[0008] The resulting current recycling is quite advantageous with regard to saving power. These and additional advantages may be better appreciated through the following detailed description.

BRIEF DESCRIPTION OF THE DRAWINGS

[0009] Figure 1A is a diagram of a two-driver system configured for current recycling according to an aspect of the disclosure.

[0010] Figure IB is a diagram of a three-driver system configured for current recycling according to an aspect of the disclosure.

[0011] Figure 2 is a circuit diagram for the two drivers of Figure 1A.

[0012] Figure 3 is a circuit diagram for the middle driver of Figure IB.

[0013] Figure 4A is a circuit diagram of a linear drop out regulator (LDO) for the system of Figure 1A in accordance with a first aspect of the disclosure.

[0014] Figure 4B is a circuit diagram of an LDO for the system of Figure 1A in accordance with a second aspect of the disclosure.

[0015] Figure 4C is a circuit diagram of an LDO for the system of Figure 1A in accordance with a third aspect of the disclosure.

[0016] Figure 5 is a circuit diagram of a multiple-output LDO for the system of Figure IB.

[0017] Figure 6 is a flowchart for a method of current recycling between a pair of drives for differential data in accordance with an aspect of the disclosure.

[0018] Embodiments of the present invention and their advantages are best understood by referring to the detailed description that follows. It should be appreciated that 2017/035525 like reference numerals are used to identify like elements illustrated in one or more of the figures.

DETAILED DESCRIPTION

[0019] To save power, a serial coupling is disclosed for a plurality of drivers for differential data output signals. A first driver couples between a power supply node supplying a power supply voltage and an intermediate voltage node. A voltage regulator such as a linear dropout regulator (LDO) charges the intermediate voltage node to an intermediate voltage that is less than the power supply voltage and greater than ground. The difference between the power supply voltage and the intermediate voltage thus represents the "voltage swing" for the first driver. In that regard, the first driver includes a pair of output nodes and a plurality of transistor switches. The transistor switches respond to a first differential data input signal. Depending upon the binary state of the first differential data input signal, the transistor switches are driven into a first configuration or into a second configuration. In the first configuration, the transistors switches are configured such that one of the output nodes couples to the power supply node such that the one output node is charged to the power supply voltage whereas a remaining one of the output nodes couples to the intermediate power node such that the remaining one of the output nodes is charged to the intermediate voltage. The second configuration is just the reverse such that the remaining one of the output nodes is charged to the power supply voltage whereas the first one of the output nodes is charged to the intermediate voltage.

[0020] The first driver's output nodes couple through respective transmission lines to a receiver such that the output nodes form a circuit through their respective transmission lines and the receiver. The output node charged to the power supply voltage will thus source a first current that flows through the receiver back to the output node charged to the intermediate voltage. The voltages for the output nodes and the corresponding direction of the first current define a first differential data output signal driven by the first driver. The first current from the first driver is recycled through the remaining drivers, which are coupled in series with the first driver. For example, in a system including just two drivers, the second driver couples between the intermediate voltage node and ground. The swing voltage for the second driver is thus defined by the difference between the intermediate voltage and ground. The second driver includes a plurality of transistor switches that respond to a binary state of a second differential data inputs signal to function analogously as discussed with regard to the first driver. A first output node for the second driver will thus be coupled to either the intermediate voltage node or to ground whereas a second output node for the second driver will be coupled in a complementary fashion. The resulting charging of one of the output nodes to the intermediate voltage causes the first current to be sourced from the charged output node through a corresponding receiver and be conducted into ground by the discharged one of the output nodes.

[0021] As noted earlier, an LDO charges the intermediate node that couples the two drivers together. This LDO has some input impedance that is much higher than the output impedance for the driver's output nodes. A negligible amount of current from the first driver will thus flow into the LDO such that it would be more accurate to indicate that the second driver conducts a second current from its output nodes that is substantially equal to the first current conducted by the output nodes of the first driver. But to a first order, the first current may be deemed to be entirely recycled by the second driver, which produces significant power savings. In that regard, it would be conventional to generate two differential data output signals using two corresponding drivers configured as discussed above for the second driver. In other words, each conventional driver would have a voltage swing between the intermediate voltage and ground. In such a conventional arrangement, the LDO must function as a resistor to the output current of its driver with regard to the voltage drop from the power supply voltage to the intermediate voltage. The resulting power consumption by the LDO is thus proportional to the driver output current. Each such conventional driver will thus have a power loss that is proportional to the current conducted by its output nodes. But the current recycling disclosed herein enables the two drivers to have the substantially the same power consumption as one conventional driver. The current recycling disclosed herein thus provides for the transmission of two differential data output signals at one half the power consumption of two corresponding conventional drivers.

[0022] Even greater power savings may be obtained by the serial coupling of three (or more) drivers as will be explained further herein. The resulting advantageous features may be better appreciated through the following example embodiments. Turning now to the drawings, Figure 1A illustrates a two-driver system 100. In system 100, a first driver 105 couples between a power supply node supplying a power supply voltage VDD and an intermediate voltage node VLDO. An LDO 155 powered by the power supply voltage VDD uses a voltage reference VREF to charge the intermediate voltage node VLDO to an intermediate voltage that is less than the power supply voltage VDD but greater than ground. It is beneficial if the magnitude of the voltage swing for first driver 105 to be the same as for a second driver 110 in which case tghe intermediate voltage would equal VDD/2 but it will be appreciated that other values may be used for the intermediate voltage. Depending upon the binary state of a first differential data input signal Dl, first driver 105 will charge one of its output nodes 115 and 120 to the power supply voltage VDD and the other to the intermediate voltage. For example, suppose output node 115 is charged to the power supply voltage VDD while output node 120 is charged to the intermediate voltage VLDO in response to the first differential data input signal Dl having a first binary value. A first current II will then flow from the power supply node through output node 115 and through a remote receiver (not illustrated) and sink back in into output node 120 output node so as to be discharged into the intermediate voltage node VLDO. Conversely, if the differential data input signal Dl has a complementary second binary state, the charging of the output nodes is reversed such that output node 120 is charged to the power supply voltage VDD and output node 115 charged to the intermediate voltage. The first current II will then be sourced by output node 120 and returned through output node 115 to be discharged into the intermediate voltage node VLDO. The charging of the output nodes for first driver 105 and the resulting direction of the first current II defines the binary state of a differential data output signal Dl driven by first driver 105 to the receiver.

[0023] Second driver 110 is coupled between the intermediate voltage node VLDO and ground. Depending upon the binary state of a differential data input signal D2, second driver 110 will charge one of its output nodes 125 and 130 to the intermediate voltage and discharge a remaining one of its output nodes to ground. A second current 12 will then flow from the intermediate voltage node VLDO out the charged output node for second driver 105 and be discharged to ground (after passing through the external receiver, not illustrated) upon returning to the discharged output node to be discharged into ground. Because of the high input impedance for LDO 155, the second current 12 is substantially equal to the first current II such that first current II is essentially recycled as second current 12.

[0024] In one aspect of the disclosure, first driver 105 may be deemed to form a first means for driving a first pair of output nodes 115 and 120 with a first differential current responsive to a first differential data input signal (Dl), the first means being coupled between the power supply node and the intermediate voltage node VLDO. Similarly, second driver 1 10 may be deemed to form a second means for driving a second pair of output nodes 125 and 130 with a second differential current responsive to a second differential data input signal (D2), the second means being coupled between the intermediate voltage node VLDO and ground in series with the first means such that the second differential current substantially equals the first differential current.

[0025] An analogous current recycling occurs in a three-driver system 150 shown in Figure IB. First driver 105 couples between the power supply node and an a first intermediate voltage node VLDOl and responds to first differential data input signal Dl to drive first differential data output signal Dl as discussed analogously with regard to system 100. Similarly, second driver 110 couples between a second intermediate voltage node VLD02 and responds to second differential data input signal D2 to drive second differential data output signal D2 as also discussed analogously with regard to system 100. However, first driver 105 is not directly in series with second driver 110. Instead, a third driver 140 intervenes between first driver 105 and second driver 110. Third driver 140 couples between the first intermediate voltage node VLDOl and the second intermediate voltage node VLD02 and responds to a third differential data input signal D3 to drive a third differential data output signal D3. A multiple-output LDO 160 charges the first intermediate voltage node VLDOl to a first intermediate voltage VLDOl and charges second intermediate voltage node VLD02 to a second intermediate voltage VLD02. The first intermediate voltage VLDOl is less than the power supply voltage VDD and greater than the second intermediate voltage VLD02, which in turn is greater than ground. As discussed with regard to system 100, it is beneficial if the swing voltage is equal for all three drivers in system 150. In such an embodiment, LDO 160 charges first intermediate voltage node VLDOl to (2/3)* VDD and charges second intermediate voltage node VLD02 to (1/3)* VDD. The swing voltage for drivers 105, 140, and 110 is thus (1/3)* VDD. But it will be appreciated that different swing voltages may be used in alternative embodiments.

[0026] Third driver 140 drives differential data output signal D3 using an output node 135 and an output node 145. Depending upon the binary value of differential data input signal D3, third driver 140 will charge one of output nodes 135 and 145 to the first intermediate voltage and a remaining one of the output nodes to the second intermediate voltage. A third current 13 will thus be sourced from the higher charged output node to be received at the output voltage with the lower voltage. Since mutliple-output LDO 160 presents a high input impedance at first intermediate voltage node VLDOl and at second intermediate voltage node VLD02, third current 13 is substantially equal to both first current II and to second current 12. First current II is thus essentially recycled through both third driver 140 and second driver 110. In contrast, if three conventional drivers were each configured to have a voltage swing of (1/3)*VDD, such a conventional system would use three times the power used by system 150. Depending upon the sensitivity of the receiver, it will be appreciated that four or more drivers may be arranged in series in alternative embodiments to achieve even greater power savings.

[0027] The transistor switches in first output driver 105 and second output driver 110 in system 100 may be arranged as shown in Figure 2. Since first driver 105 drives one of its output nodes to the power supply voltage VDD, the transistor switches in first driver 105 may all comprise PMOS transistors. In particular, first driver 105 includes a pair of PMOS transistors I and P2 both having their source coupled to a power supply node supplying the power supply voltage VDD. Since the input data signal Dl is differential, it is represented by a positive differential input data signal DlPin and a negative differential input data signal DlNin. Input signal DlPin drives the gate of transistor PI whereas input signal DlNin drives the gate of transistor P2. The drains for transistors PI and P2 each couple to a respective load resistor RL. In general, the resistance RL may match the characteristic impedance of the transmission line coupling an output node to the receiver (not illustrated). The drain of transistor PI couples to an output node DINout 120 through its load resistor RL whereas the drain of transistor P2 couples to an output node DIPout 115 through its load resistor RL. U 2017/035525

Output node DlNout 120 couples through another load resistor RL to a source of a PMOS transistor P3. Similarly, output node DlPout 115 couples through another load resistor RL to a source of a PMOS transistor P4. Input signal DlPin drives the gate of transistor P4 whereas input signal DINin drives the gate of transistor P3. The drains for transistors P3 and P4 both couple to the intermediate voltage node VLDO.

[0028] If the differential data input signal DlPin is sufficiently higher the differential data input signal DINin (e.g., higher by at least a threshold voltage for the PMOS

transistors), transistors P2 and P3 will be conducting and transistors PI and P4 will be off such that output node DlPout 115 is charged towards the power supply voltage VDD while output node DlNout 120 is charged towards the intermediate voltage VLDO. The first current II (Figure 1 A) will then be sourced by output node DlPout 115 and received at output node DlNout 120. Conversely, if the differential data input signal DINin is sufficiently higher in voltage than the differential data input signal DlPin, transistors PI and P4 will be conducting and transistors P2 and P3 will be off such that output node DlNout 120 is charged towards the power supply voltage VDD while output node DlPout 115 is charged toward the intermediate voltage VLDO. In that case, the first current II is sourced by output node DlNout 120. In both cases (assuming that the load resistance RT is matched to the transmission line), the first current II equals Vswing/4*RL, where Vswing = (VDD - VLDO) . For example, when output node DlPout 115 is sourcing the first current II, the load resistor RL at the drain of transistor P2 is in series with the load resistance RL for the transmission line on the way to the receiver. The first current II then returns from the receiver to output node DlNout 120 such that the load resistance RL for the transmission line is in series with the load resistor RL at the source of transistor P3. The total resistance faced by the first driver current II is thus 4*RL. [0029] Since second driver 110 discharges one of its output nodes towards ground, the transistor switches in second driver 110 may all comprise NMOS transistors. In particular, second driver 110 includes a pair of NMOS transistors Ml and M2 each having their drain coupled to the intermediate voltage node VLDO. Differential data input signal D2 is represented by a differential data input signal D2Pin and a differential data input signal D2Nin. The differential data input signal D2Pin drives the gate of transistor Ml whereas the differential data input signal D2Nin drives the gate of transistor M2. The source of transistor Ml couples through a load resistor RL to an output node D2Pout 125. Similarly, the source of transistor M2 couples through a load resistor RL to an output node D2Nout 130. Output node D2Pout 125 couples through another load resistor RL to the drain of an NMOS transistor M3 having its source coupled to ground. Output node D2Nout 130 couples through another load resistor RL to the drain of an NMOS transistor M4 having its source coupled to ground. Differential data input signal D2Pin drives the gate of transistor M4 whereas differential data input signal D2Nin drives the gate of transistor M3. Depending upon the binary state of differential data input signal D2, either transistors Ml and M4 will be conducting while transistors M2 and M3 are off or transistors M2 and M3 will be conducting while transistors Ml and M4 are off. One of output node 125 and 130 will thus be charges towards the first intermediate voltage VLDO while a remaining one of output nodes 125 and 130 will be discharged towards ground. The charged output node will then source the second driver current 12 (Figure 1 A) while the discharge output node receives the second driver current T2. Assuming that the load resistors RL are matched to the transmission line impedance, the second driver current 12 equals VLDO/4RT. If VLDO equals one half of the power supply voltage VDD, the first driver current II will be essentially equal to the second driver current 12 such that the first driver current II is recycled as the second driver current 12. [0030] System 150 is shown in more detail in Figure 3. First driver 105 may be formed as discussed with regard to Figure 2 except that the intermediate voltage node VLDO is replaced by the first intermediate voltage node VLDOl. Similarly, second driver 110 may be formed as discussed with regard to Figure 2 except that the intermediate voltage node VLDO is replaced by the second intermediate voltage node VLD02. In contrast to first output driver 105 and to second output driver 110, third output driver 140 does not drive its output nodes to the power supply voltage VDD nor to ground but instead to the intermediate voltages VLDOl and VLD02. The switches in third output driver 140 may thus be formed using transmission gates so as to adequately pass these two intermediate voltages. For example, third output driver 140 includes a first transmission gate formed by an MOS transistor M5 and a PMOS transistor P5. The source of transistor P5 and the drain of transistor M5 both couple to the first intermediate voltage node VLDOl. The drain of transistor P5 and the source of transistor M5 couple through a load resistor RL to an output node D3Pout 145. Differential data input signal D3 is represented by a differential data input signal D3Pin and a differential data input signal D3Nin. The differential data input signal D3Pin drives the gate of transistor P5 whereas the differential data input signal D3Nin drives the gate of transistor M5. The first transmission gate will thus be closed when differential data input signal D3Nin is sufficiently higher in voltage than differential data input signal D3Pin. In that case, output node D3Pout 145 is charged towards the first intermediate voltage VLDOl and sources the third driver current 13. Conversely, when the differential data input signal D3Pin is sufficiently higher in voltage than the differential data input signal D3Nin, the first transmission gate is closed.

[0031] Third output driver 140 include a second transmission gate formed by an NMOS transistor M6 and a PMOS transistor P6. The source of transistor P6 and the drain of transistor M6 both couple to the first intermediate voltage node VLDOl. The drain of transistor P6 and the source of transistor M6 couple through a load resistor RL to an output node D3Nout 135. The differential data input signal D3Pin drives the gate of transistor P5 whereas the differential data input signal D3Nin drives the gate of transistor M5. The second transmission gate will thus be closed when differential data input signal D3Pin is sufficiently higher in voltage than differential data input signal D3Nin. In that case, output node D3Nout 135 is charged towards the first intermediate voltage VLDOl and sources the third driver current 13. Conversely, when the differential data input signal D3Nin is sufficiently higher in voltage than the differential data input signal D3Pin, the second transmission gate is closed.

[0032] Output node D3Pout 145 couples through another load resistor RL to a third transmission gate formed by an MOS transistor M7 and a PMOS transistor P7. The source of transistor P7 and the drain of transistor M7 both couple through their load resistor RL to the output node D3Pout 145. The drain of transistor P7 and the source of transistor M7 couple to the second intermediate voltage node VLD02. The differential data input signal D3Pin drives the gate of transistor M7 whereas the differential data input signal D3Nin drives the gate of transistor P7. In contrast to the first transmission gate, the third transmission gate will thus be open when differential data input signal D3Nin is sufficiently higher in voltage than differential data input signal D3Pin.

[0033] Finally, output node D3Nout 135 couples through another load resistor RL to a fourth transmission gate formed by an NMOS transistor M8 and a PMOS transistor P8. The source of transistor P8 and the drain of transistor M8 both couple through their load resistor RL to the output node D3Nout 135. The drain of transistor P8 and the source of transistor M8 couple to the second intermediate voltage node VLD02. The differential data input signal D3Nin drives the gate of transistor M8 whereas the differential data input signal D3Pin drives the gate of transistor P8. In contrast to the second transmission gate, the fourth transmission gate will thus be closed when differential data input signal D3Nin is sufficiently higher in voltage than differential data input signal D3Pin.

[0034] Some example linear dropout regulators will now be discussed. For example, LDO 155 (Figure 1A) may be implemented in a number of ways such as shown for an LDO 400 in Figure 4A. A differential amplifier 410 amplifies the difference between the reference voltage Vref and the intermediate voltage VLDO to maintain the intermediate voltage VLDO equal to the reference voltage Vref. In LDO 400, a reference voltage source (not illustrated) would thus maintain the reference voltage Vref at VDD/2 to maintain the intermediate voltage VLDO at VDD/2 in one embodiment.

[0035] Alternatively, LDO 1 5 may be implemented as shown for LDO 405 in

Figure 4B. A PMOS transistor P9 has its source coupled to the power supply voltage node for supplying the power supply voltage VDD. The drain of transistor P9 functions as the intermediate voltage output node VLDO, which in turn couples through a voltage divider formed by a serial combination of a resistor Rl and a resistor R2 to ground. The voltage divider forms a feedback voltage. Differential amplifier 410 amplifies the difference between the reference voltage Vref and the feedback voltage to drive the gate of transistor P9. If the resistance of resistor R l equals the resistance of resistor R2 and if the reference voltage Vref is VDD/4, the intermediate output voltage VLDO will thus equal VDD/2.

[0036] In addition, LDO 155 may be implemented as shown for LDO 415 in Figure 4C. An NMOS transistor M9 has its source coupled to the ground. The drain of transistor M9 functions as the intennediate voltage output node VLDO, which in turn couples through a voltage divider formed by a serial combination of a resistor Rl and a resistor R2 to the power supply voltage node. The voltage divider forms a feedback voltage. Differential amplifier 410 amplifies the difference between the reference voltage Vref and the feedback voltage to drive the gate of transistor M9. If the resistance of resistor Rl equals the resistance of resistor R2 and if the reference voltage Vref is (3/4)*VDD, the intermediate output voltage VLDO will thus equal VDD/2.

[0037] Multiple-output LDO 160 is shown in more detail in Figure 5. LDO 415 is configured analogously as discussed with regard to Figure 4C to produce the first intermediate voltage VLDOl . To maintain the first intermediate voltage at (2/3)*VDD, the reference voltage for LDO 415 may be maintained at (5/6)*VDD. Similarly, LDO 405 is configured analogously as discussed with regard to Figure 4B to produce the second intermediate voltage VLD02. To maintain the second intermediate voltage at (1/3)*VDD, the reference voltage for LDO 405 may be maintained as (1/6)*VDD. The source of transistor M9 in LDO A 15 couples to the source of transistor P9 in LDO 405. For additional stability, LDO 400 is configured to drive the sources of transistors M9 and P9 with a mid- range intermediate voltage such as equal to VDD/2. In that case, the reference voltage for LDO 400 would also be equal to VDD/2.

[0038] Regardless of the number of drivers in a given embodiment, note that the common-mode voltage for each corresponding differential data output signal is different. The receiver (not illustrated) may thus receive each differential data output signal through an AC coupling to filter out the different common-mode voltages. An example method of operation for current recycling in differential output drivers will now be discussed.

[0039] An example method of operation for current recycling is provided by the flowchart of Figure 6. The method includes an act 600 of charging a first voltage node to a first intermediate voltage. The charging of intermediate voltage node VLDO by LDO 400 in system 100 or the charging of the sources for transistors P9 and M9 by LDO 400 in system 150 is an example of act 600.

[0040] The method also includes an act 605 that is responsive to a first binary state of a first differential data input signal and includes coupling a first output node for a first driver to a power supply node charged to a power supply voltage while sourcing a first current from the first output node and coupling a second output node for the first driver to the first voltage node while sinking the first current from the second output node into the first voltage node, wherein the power supply voltage is greater than the first intermediate voltage. An example of act 605 in system 100 is the coupling of output node DlPout 115 to the power supply node through transistor P2 in first driver 105 to source the first current from output node DlPout 11 while coupling output node DINin 120 through transistor P3 to the intermediate voltage node VLDO to sink the first current into output node DINin 120. The same act is repeated by first driver 105 in system 150 except that the intermediate voltage node VLDO is replaced by the source nodes for transistors P9 and M9.

[0041] Finally, the method includes an act 610 that is responsive to a first binary state of a second differential data input signal and includes coupling a third output node for a second driver to the first voltage node while sourcing a second current from the third output node and coupling a fourth output node for the second driver to a second voltage node charged to a second intermediate voltage while sinking the second current from the fourth output node into the second voltage node, wherein the first intermediate voltage is greater than the second intermediate voltage; and wherein the second current is substantially equal to the first current. An example of act 610 in system 100 is the coupling of output node D2Pout 125 to the intermediate voltage node VLDO through transistor Ml in second driver 110 to source the second current from output node D2Pout 125 while coupling output node D2 in 130 through transistor M4 to ground to sink the first current into output node D2Nin 130. In system 100, the second intermediate voltage of act 610 is thus ground. Another example of act 610 is in system 150 occurs when the first transmission gate (transistors M5 and P5) couples output node D3Pout 145 to the first intermediate voltage node VLDOl to source the third current while the fourth transmission gate (transistors P8 and M8) couples output node D3Nout 135 to the second intermediate voltage node VLD02 to sink the third current. The second intermediate voltage of act 610 in system 150 is thus VLDO.

[0001] As those of some skill in this art will by now appreciate and depending on the particular application at hand, many modifications, substitutions and variations can be made in and to the materials, apparatus, configurations and methods of use of the devices of the present disclosure without departing from the scope thereof. In light of this, the scope of the present disclosure should not be limited to that of the particular embodiments illustrated and described herein, as they are merely by way of some examples thereof, but rather, should be fully commensurate with that of the claims appended hereafter and their functional equivalents.