With reference to FIG. 1, in a typical superheterodyne radio transceiver, image rejection is required. In the radio transmitter, a baseband signal or intermediate frequency signal is upconverted to a higher RF frequency for transmission. The upconversion is typically realized with a mixer, and in some radio architectures it is followed by an external filter (not shown) to remove the undesired image. For example, when a signal at an intermediate frequency tip (derived from the baseband signal to be transmitted) is to be upconverted to a higher frequency, the analog multiplier (also known as a mixer) 10 and an oscillator 12 with frequency fLo are employed for frequency upconversion. The upper sideband frequency fLo+fF and the lower sideband frequency fLO-fIF, are generated as a result of the mixing process. One of the sideband frequencies is the desired signal fRF, while the other one is the unwanted image frequency fiM. The goal of an upconversion process is to maintain or amplify the signal level at fRF while the image signal at fjm is to be attenuated as much as possible. This suppression of the image frequency fiM is called"image rejection."If fLo+fF is the desired frequency, then lower sideband rejection is required. Similarly, if fLO-fIF is the desired frequency, upper sideband rejection is required.

At high radio frequencies, a low-side oscillator fLo is usually preferred because it is easier to obtain better oscillator performance than a high-side oscillator. Consequently, the desired sideband is located at fLO+fIF while the undesired image sideband is at fLO-fIF. To suppress the image, a high-pass filter having a response as shown in FIG. 2 may be used. Costly off-chip bandpass filters are commonly employed to pass the desired sideband while rejecting the undesired image signal. Also, image reject mixer topologies are used for this purpose. However, image reject mixers typically require significantly more circuitry and power consumption of a conventional mixer.

Today, radio communication devices may support multiple frequency bands. For example, the IEEE 802. 1 la and b standards for wireless local area

network (WLAN) applications operate in different frequency bands. The IEEE 802. 11 a standard operates in the 5 GHz band (5.15-5. 35 GHz and 5.47-5. 875 GHz), while 802.1 lb operates in the 2.4 GHz band (2.4-2. 4825 GHz). Therefore, in a radio transceiver that operates in both bands, a different image reject filter is required for each band, thus increasing the cost.

A similar situation exists in cellular telephony where, for example, multimode phones for GSM/PCS/DCS are required. Clearly to save integrated circuit area it is highly desirable to have circuits which are usable at various frequency bands without duplicative circuitry. A tunable upconverter mixer would save significant silicon area on an integrated circuit used in these applications and reduce power consumption needs, and no such solution is heretofore known.

SUMMARY OF THE INVENTION Briefly, tunable upconversion mixers are provided that have a controllable passband response and provide substantial image rejection, making costly post- mixing filtering at least optional, if not unnecessary for many applications. A single mixer is able to support several frequency bands (and/or be accurately tuned within one frequency band) by means of varying the capacitance in a tunable load circuit for the mixer circuit. The tunable mixer comprises a mixer circuit having inputs for receiving a signal to be upconverted and an oscillator signal to be mixed with the signal to be upconverted. The mixer generates a mixer output signal at a desired sideband frequency and an image signal at an image frequency. A tunable load circuit is coupled to the mixer circuit and responsive to a control signal to resonate and pass signals in a desired passband corresponding to the mixer output signal at the desired sideband frequency, and which attenuates signals in an attenuation band outside the desired passband that includes the image signal at the undesired image frequency.

The above and other objects and advantages will become more readily apparent when reference is made to the following description taken in conjunction with the accompanying drawings.

BRIEF DESCRIPTION OF THE DRAWINGS FIG. 1 is a block diagram showing a typical arrangement for an upconversion mixer to upconvert a signal to a radio frequency (RF) signal.

FIG. 2 is a frequency domain diagram that shows the desired and undesired signals generated in a frequency upconversion process.

FIG. 3 is a schematic diagram of a tuned upconversion mixer.

FIG. 4 is a frequency domain diagram that shows how the tuned upconversion mixer of FIG. 3 achieves image rejection.

FIG. 5 is a schematic diagram of a digitally tunable upconversion mixer.

FIG. 6 is a schematic diagram of a tunable upconversion mixer with a voltage-controlled tunable load.

FIG. 7 is a schematic diagram of a tunable upconverter including a tunable mixer of FIG. 5 or FIG. 6.

FIG. 8 is a schematic diagram of a tuned upconverter that features a tuned or tunable pre-amplifier.

FIG. 9 is a block diagram of a multiple-band radio transmitter having multiple transmit paths, wherein a single tunable upconverter is used in each transmit path instead of multiple upconverters each for a designated frequency band.

DETAILED DESCRIPTION OF THE DRAWINGS With reference to FIGs. 3 and 4, a generalized schematic diagram for a tuned upconverter mixer 100 is shown. The tuned upconverter mixer 100 comprises a mixer circuit 110 and a tuned load circuit 120. The mixer circuit 110 is, for example, a double balanced Gilbert cell having a differential input transistor pair Ql and Q2 and a"quad"of switching transistors Q3, Q4, Q5 and Q6. The input signal VIF is applied to the bases of Ql and Q2. The local oscillator signal VLO is applied to the bases of the"quad"transistors to generate the mixing action. The upconverted Vu output is obtained at the cross-coupled collectors of Q3, Q4, Q5 and Q6. This output contains both sidebands as well as other frequencies originating from the mixing process. The concept of a tuned load can be applied to any type of mixer circuit, such as a single ended mixer circuit version of that shown

in FIG. 3, or any other suitable mixer circuit. The tuned load circuit 120 is realized by inductor loads LL coupled to the collectors of the switching transistors Q3, Q4, Qs and Q6, and a capacitor load CL (also hereinafter called a capacitance circuit) coupled between the inductor loads LL. In this manner inductor loads LL and the capacitor load CL form a parallel LC resonant circuit.

For simplicity, it is assumed that the upper sideband (fu = fLO+flF), is the desired signal and the lower sideband (fiM = fLO-fIF) is the undesired image. It is desirable to pass the upper sideband while rejecting the lower sideband. The mixer 100 is tuned to have strong gain at the desired sideband frequency while attenuating the undesired image frequency, thereby providing image rejection.

The tuned load circuit 120 shown in FIG. 3 is second-order. A higher order filter/resonator can be used for more complex filtering requirements. It is generally desirable to reject the image as early as possible to prevent noise injection caused by the image signal.

By adjusting the values for LL and/or CL (as described below in conjunction with FIGs. 5 and 6), the tuned load circuit 120 is made to resonate at a controlled or selectable desired sideband frequency to provide maximum passband gain, while out-of-band signals, such as the undesired image, are attenuated as shown in FIG.

4. The capacitive loading from the next stage (e. g., pre-amplifier) may be absorbed in the capacitor CL. In addition to image rejection, the inductive loads LL also provide better voltage headroom and hence improve linearity for the circuit.

FIGs. 5 and 6 illustrate two exemplary types of tunable mixers, each of which is suitable for use in multi-band or (single band) tunable frequency upconversion applications. These exemplary tunable mixers can process a signal for upconversion to a selectable frequency in one or more bands that would otherwise require mixers dedicated and tuned to each frequency range or band.

Turning to FIG. 5, a tunable mixer 200 is shown having a tunable load circuit 130 comprising a capacitance circuit 132 in form of a bank of one or more capacitors (Cl to Cn) connected between the inductors LL to form the effective capacitance CL (FIG. 3) and one or more switches Si to Sn. Switches Si to Sn are controlled to switch individual capacitors Cl to Cn in the capacitance circuit 132 in and out of the tunable load circuit 130 as necessary to tune the tunable load circuit

130 of the mixer 200 to the desired resonance frequency (FIG. 4). Signals sourced from an interface (e. g. , serial port) usually driven by a baseband chip control the switches Si to Sn to achieve the desired frequency band of operation. The source of the control signals for the bank of capacitors is generally indicated by the control block 134 shown in FIG. 5. Therefore, instead of using multiple mixers each of which is dedicated to a different frequency band, a single mixer circuit can be used for the multiple frequency bands to save integrated circuit area.

FIG. 6 illustrates a tunable mixer 300 having a tunable load circuit 140 in which tuning is realized by means a capacitance circuit 142 comprising two varactors Cv connected in a balanced manner to inductors LL to form a parallel resonant circuit. The varactors Cv in the capacitance circuit 142 are responsive to a control voltage signal Vcm applied to a node between them. The voltage control signal Vctl controls the capacitance of the varactors Cv to tune the mixer to the desired frequency band. The voltage control signal Vctl may be a direct current voltage signal that can be digitally switched/varied or continuously varied. Digital switching gives better noise performance, while continuous adjustment provides more tuning flexibility. While two varactors are shown, it should be understood that more than two varactors may be used.

As a further alternative, a tunable load circuit may use a combination of the features of the capacitance circuits 132 and 142 circuits shown in FIGs. 5 and 6.

For example, a capacitance circuit may include a bank of capacitors for coarse tuning and one or more varactors for fine tuning.

If the mixer circuit 110 were a single-ended mixer circuit, then transistors Q2, Q5 and Q6 would be eliminated, and the tunable load circuit 120 would comprise inductors LL connected to the collectors of transistors Q3 and Q4 and the capacitance circuit would comprise a bank of one or more capacitors (FIG. 5) or one or more varactors (FIG. 6) coupled across the collectors of those same transistors.

In operation, the tunable load circuits of the mixers of FIGs. 5 and 6 are responsive a control signal to resonate and pass signals at a desired passband corresponding to the mixer output signal at the desired sideband frequency. The tunable load circuits also attenuate signals in an attenuation band outside the

desired passband that includes the image signal at the undesired image frequency.

The tunable load circuits are tuned by adjusting the capacitance in the parallel resonant LC circuits by way of the capacitance circuits shown in FIGs. 5 and 6, respectively.

The tunable mixers shown in FIGs. 5 and 6 will provide image rejection, that for many applications, will be sufficient to forego the need for separate on-chip or off-chip image rejection filters. Even if a particular radio design may call for image rejection filters, the tunable mixer described herein may still be useful because it provides control to tune the frequency location of the passband, whereas a fixed image reject filter does not. If as a result of semiconductor process variances, a separate image reject filter does not provide sufficient image rejection, adjustment can be made by way of a tunable mixer. Thus, still a further benefit of the tunable mixers described above is the ability to adjust for frequency migration caused by semiconductor process variations.

FIG. 7 shows an upconverter network 500 comprising either the tunable mixer 200 or tunable mixer 300, a pre-amplifier 400 and a balanced-to-unbalanced transformer Tl (also known as balun). Depending on the requirements for a particular application, a single LC tuned mixer may not provide sufficient image rejection. Since the tunable mixer 200 or 300 is connected to a pre-amplifier 400 to drive a power amplifier, image rejection capability may be added to the pre- amplifier 400. The pre-amplifier 400 consists of a differential pair of transistors Q7 and Q8, for example. The balun Tl consists of Np turns in a primary winding and Ns turns in a secondary winding. A tunable load circuit for the pre-amplifier 400 is formed by capacitance circuit 132 or 142 (FIGs. 5 and 6, respectively) connected in parallel with an inductance that is provided by the primary of the balun Tl. The number of turns in the windings of the balun T1 depends on the desired output impedance. The center tap of the primary of the balun is used to feed the Vcc supply for the pre-amplifier, thus increasing the voltage headroom.

The balun Tl converts the differential signal at the pre-amplifier output to a single-ended signal (VRF). By controlling the capacitance of the capacitance circuit 132 or 142 using the methods described above in conjunction with FIGs. 5 and 6, the frequency of resonance can be centered to the desired frequency of operation.

Hence, the pre-amplifier 160, loaded with the tuned balun T1, will exhibit a passband response, centered at the desired RF frequency and therefore reject the undesired image. This is the same image rejection mechanism referred to in conjunction with the LC-tuned mixer previously described.

In response to tuning control signals, the tunable upconverter of FIG. 7 selectively tunes both a load circuit on the mixer and a load circuit on the pre- amplifier to allow for increased image rejection in multiple bands. Furthermore, it is possible to use in a capacitance circuit a combination of switched capacitors and varactors to realize the tuning, as suggested above, wherein the bank of switched capacitors is used for coarse tuning and the varactors are used for fine tuning. The tunable upconverter 500 has the additional benefit of eliminating the need for image rejection filters after the upmixing process. By tuning the pre-amplifier to the desired RF frequency, signals outside the bandwidth of the pre-amplifier tunable load will be attenuated. Consequently, for example, in a transmitter, the bandpass filter for each frequency band (which in some cases must be implemented off-chip) that may follow an upconverter is not needed. However, for some <BR> <BR> applications, image reject (e. g. , bandpass filters) may still be needed depending on<BR> \ the image rejection requirements for the application of the radio.

With reference to FIG. 8, an upconverter 600 is shown comprising the tuned mixer 100, the pre-amplifier 400, the balun Tl, and the capacitance circuit 132 or 142 connected in parallel with the primary of the balun T1. The upconverter 600 is not tunable to handle operation in multiple frequency bands, but it has tuned mixer and a tuned or tunable pre-amplifier. The load circuit on the pre-amplifier 400 consisting of a parallel LC resonant circuit may be fixed, or adjustable. If the pre- amplifier load circuit is to be fixed, a single capacitor can be used, instead of the adjustable capacitance circuits 132 and 142. If the load circuit is to be adjustable, then the capacitance circuit 132 or 142 is used (or a combination thereof), but since upconverter 600 is not tunable for operation in multiple frequency bands, the degree of tuning of the pre-amplifier load circuit need not be to the same degree as that used in the upconverter 500 of FIG. 7. Nevertheless, as suggested above, there is great utility in being able to the tune pre-amplifier load circuit after a semiconductor fabrication process if the tuned mixer 100 and/or other image reject

filters do not provide the desired image rejection due to variations caused by the fabrication process.

The capability to reduce the number of components as well as eliminate off- chip components in a radio transmitter has significant impact in the design and cost of a multiple-input multiple-output (MIMO) radio. In a MIMO radio, there are multiple transmitter paths to transmit multiple signals simultaneously. FIG. 9 shows the RF portion of a 2-path MIMO radio transmitter 700, as an example. The baseband or IF signals to be transmitted may be two different data streams, or weighted components of one data stream, to be transmitted simultaneously by two antennas. The transmitter 700 shown in FIG. 9 can transmit signals in either of two radio frequency bands (RFB 1 and RFB2), such as the 2.4 GHz band and one of the 5 GHz UNII bands, for example.

The transmitter 700 comprises in each transmitter path, a variable gain amplifier 710 to adjust the gain of each baseband or IF signal to be transmitted, an upconverter 500 (as shown in FIG. 7), a power amplifier 720 for RFB1 and a power amplifier 730 for RFB2. Band-select switches 750 and 760 are coupled between the output of the power amplifiers in the respective transmitter paths and a corresponding one of the antennas 770 and 780. In general, there may be a separate power amplifier for each of the frequency bands supported in each transmitter path.

If a separate mixer were needed for each band, then for the case of FIG. 9, a total of four mixers would be needed, together with the associated supporting circuitry and filters. Moreover, if the MIMO transmitter were capable of supporting four transmit paths (which may be desirable for some MIMO applications), then 8 mixers would be needed. By providing a tunable upconverter 500, a single upconverter can be used for each transmitter path for both frequency bands. Furthermore, if the transmitter operates in 3 bands, then in each transmitter path a single tunable upconverter would be replacing 3 mixers. In a MIMO radio, where multiple transmitter (and receiver) paths are required, an upconverter network that has multiple uses can contribute significantly in reducing the silicon area in an integrated circuit MIMO radio implementation.

Furthermore, by using the tunable upconverter 500, there is no need to go off-chip for post-mixing filtering in a superheterodyne transmitter architecture.

Therefore, as shown by the dotted line in FIG. 9, all of the elements from the variable gain amplifier 710 to the power amplifier 720 or 730 can be implemented in the same integrated circuit, which further reduces the cost of the radio.

One application of the tunable mixers described herein is the 5GHz bands for the IEEE 802.11 a and the 2.4 GHz band for the IEEE 802.1 lb for wireless local area network (WLAN) applications. However, it should be understood that the tunable mixer concepts can be applied to any multi-band or variable band application.

To summarize, a tunable mixer is provided comprising a mixer circuit and a tunable load circuit. The mixer circuit has inputs for receiving a signal to be upconverted and an oscillator signal to be mixed with the signal to be upconverted.

The mixer generates a mixer output signal at a desired sideband frequency and an image signal at an image frequency. A tunable load circuit is coupled to the mixer circuit and is responsive to a control signal to resonate and pass signals in a desired passband corresponding to the mixer output signal at the desired sideband frequency, and which attenuates signals in an attenuation band outside the desired passband that includes the image signal at the image frequency. A tunable upconverter is provided that includes the mixer and further includes a pre-amplifier and a pre-amplifier tunable load circuit. The pre-amplifier is coupled to the output of the mixer circuit to increase the power of the mixer output signal. The pre- amplifier tunable load circuit is coupled to the output of the pre-amplifier and is responsive to a control signal to resonate and pass signals in the desired passband, and which attenuates signals in the attenuation band.

Also provided is an upconverter with image rejection capabilities, comprising a mixer circuit having inputs for receiving a signal to be upconverted and an oscillator signal to be mixed with the signal to be upconverted. The mixer generates a mixer output signal at a desired sideband frequency and an image signal at an image frequency. A mixer tuned load circuit is coupled to the mixer circuit that resonates and passes signals in a desired passband corresponding to the mixer output signal at the desired sideband frequency, and attenuates signals in an

attenuation band that includes the image signal at the undesired image frequency.

A pre-amplifier is coupled to the output of the mixer circuit to increase the power of the mixer output signal, wherein the pre-amplifier outputs a pre-amplified signal.

A pre-amplifier tuned load circuit coupled to the output of the pre amplifier to resonate and pass signals in the desired passband and, which attenuates signals in the attenuation band.

Still further provided is a radio transmitter comprising at least first and second transmitter paths each coupled to an associated antenna to process a signal for substantially simultaneous transmission. Each of the first and second transmitter paths comprises a tunable upconversion mixer that receives as input a baseband or intermediate frequency signal to be upconverted, a local oscillator signal and a tuning control signal, and which upconverts the baseband or intermediate frequency signal to a frequency based on a frequency of the local oscillator signal and in response to the tuning control signal. The tunable upconversion mixer resonates to pass signals in a desired passband corresponding to a desired sideband frequency, and attenuates signals in an attenuation band that includes an image signal at an undesired image frequency. At least one power amplifier is coupled to the output of the tunable upconversion mixer to amplify the upconverted signal and couple an amplified signal to an associated antenna.

The above description is intended by way of example only.